Broadcasting signal transmission device, broadcasting signal reception device, and method for transmitting/receiving broadcasting signal using same

ABSTRACT

Disclosed is a broadcasting signal transmission device, a broadcasting signal reception device, and a method for transmitting/receiving a broadcasting signal using same. The method for receiving the broadcasting signal comprises the following steps: receiving the broadcasting signal, which includes a transmission frame, wherein the transmission frame includes a plurality of PLPs, which transmit components that constitute a broadcasting service, first signaling information and second signaling information, which include the signaling information of the plurality of PLPs, a first preamble signal, which has been signaled with a preamble format, and a second preamble signal, which has been signaled with pilot pattern information, wherein one of the plurality of PLPs is a base PLP, which includes a program number that corresponds to the broadcasting service and program map table information, which has been signaled with identifying information for each of the PLPs; demodulating the broadcasting signal based on the first and the second preamble signals; FEC decoding the demodulated broadcasting signal; and identifying a PLP group that includes the plurality of PLP from the FEC decoded broadcasting signal based on the first and the second signaling information, decoding at least one PLP of the identified PLP group, and providing the broadcasting service.

This application is a continuation-in-part of U.S. patent applicationSer. No. 13/884,786 filed on May 10, 2013, which is the National Phaseof PCT International Application No. PCT/KR2011/001257 filed on Feb. 23,2011, which claims the priority of U.S. Provisional Application61/307,423, filed on Feb. 23, 2010, each of which is hereby incorporatedby reference as if fully set forth herein.

FIELD OF THE INVENTION

The present invention relates to a broadcast signal transmittingapparatus for transmitting a broadcast signal, a broadcast receivingapparatus for receiving a broadcast signal, and a method of transmittingand receiving a broadcast signal and, most particularly, to an apparatusand method for transmitting and receiving a mobile broadcast signal.

BACKGROUND ART

As the time has neared to end (or terminate) the transmission of analogbroadcast signals, diverse technologies for transmitting and receivingdigital broadcast signals are being researched and developed. Herein, adigital broadcast signal may include high capacity video/audio data ascompared to an analog broadcast signal, and, in addition to thevideo/audio data, the digital broadcast signal may also include diverseadditional data.

More specifically, a digital broadcasting system for digitalbroadcasting may provide HD (High Definition) level images,multiple-channel sound (or audio), and a wide range of additionalservices. However, a data transmission efficiency for transmitting highcapacity data, a robustness of transmitting and receiving network, andflexibility in a network considering mobile receiving equipments arestill required to be enhanced.

As analog broadcast signal transmission comes to an end, varioustechnologies for transmitting/receiving digital broadcast signals arebeing developed. A digital broadcast signal may include a larger amountof video/audio data than an analog broadcast signal and further includevarious types of additional data in addition to the video/audio data.

That is, a digital broadcast system can provide HD (high definition)images, multi-channel audio and various additional services. However,data transmission efficiency for transmission of large amounts of data,robustness of transmission/reception networks and network flexibility inconsideration of mobile reception equipment need to be improved fordigital broadcast.

DETAILED DESCRIPTION OF THE INVENTION Technical Objects

Accordingly, an object of the present invention is to provide abroadcast signal transmitting apparatus and a broadcast receivingapparatus that can transmit and receive additional broadcast signals, amethod for transmitting and receiving additional broadcast signals, byusing an RF signal of a conventional broadcasting system without havingto ensure any additional frequency.

Another object is to provide a broadcast signal transmitting apparatusand a broadcast receiving apparatus that can transmit and receive mobilebroadcast signals, a method for transmitting and receiving mobilebroadcast signals, by using an RF signal of a conventional broadcastingsystem without having to ensure any additional frequency.

Yet another object of the present invention is to provide a broadcastingsignal transmission device, a broadcasting signal reception device, anda method for transmitting/receiving a broadcasting signal using the samethat can distinguish data corresponding to a service for each component,and transmit the corresponding data to each component through separatePLPs, so that the transmitted data can be received and processed.

Yet another object of the present invention is to provide a broadcastingsignal transmission device, a broadcasting signal reception device, anda method for transmitting/receiving a broadcasting signal using the samethat can signal signaling information required for servicing abroadcasting signal.

A further object of the present invention is to provide a broadcastingsignal transmission device, a broadcasting signal reception device, anda method for transmitting/receiving a broadcasting signal using the samethat can signal signaling information, so that a broadcasting signal canbe received in accordance with a receiver characteristic.

An object of the present invention is to provide an apparatus and methodfor transmitting broadcast signals to multiplex data of a broadcasttransmission/reception system providing two or more different broadcastservices in a time domain and transmit the multiplexed data through thesame RF signal bandwidth and an apparatus and method for receivingbroadcast signals corresponding thereto.

Another object of the present invention is to provide an apparatus fortransmitting broadcast signals, an apparatus for receiving broadcastsignals and methods for transmitting and receiving broadcast signals toclassify data corresponding to services by components, transmit datacorresponding to each component as a data pipe, receive and process thedata

Still another object of the present invention is to provide an apparatusfor transmitting broadcast signals, an apparatus for receiving broadcastsignals and methods for transmitting and receiving broadcast signals tosignal signaling information necessary to provide broadcast signals.

Technical Solutions

In order to achieve the above-described technical objects of the presentinvention, according to an aspect of the present invention, a method oftransmitting service data may comprise proceeding with input data tooutput transmission unit data, encoding the transmission unit data,interleaving the encoded transmission unit data, mapping the interleavedtransmission unit data, building signal frames including the mappedtransmission unit data, modulating the signal frames by OFDM (OrthogonalFrequency Division Multiplex) scheme, transmitting the modulated signalframes. Herein, the modulated signal frames have different frame typesin time domain, and the different frame types of signal frames aremultiplexed in a super frame, which is a set of the signal frames. Andherein, the modulated signal frames further include signaling data andthe signaling data have information on the different frame types.

Effects of the Invention

According to the present invention, a transmitter may performtransmission by generating a PLP for each component configuring aservice, and a receiver may identify and decode the PLP, which isreceived for each component. Thus, the present invention may respond tothe mobile broadcast communication environment with more flexibility.

The transmitter of the present invention may distinguish one componentas a component of a base layer and as a component of at least oneenhancement layer, and may transmit the distinguished component. And,the receiver may decode only the component of the base layer so as toprovide an image with basic picture quality, or the receiver may decodethe component of the base layer along with the component of at least oneenhancement layer so as to provide an image with higher picture quality.Thus, the present invention may provide images having diverse picturequalities in accordance with the receiver characteristic.

In the present invention, a transmitting end demuxes (or demultiplexes)data and a receiving end muxes (or multiplexes), so that optimalperformance can be gained when applying an LDPC codeword having a lowercode rate to the broadcasting/communication system. Thus, an optimalerror correction performance of the LDPC may be gained even at a lowercode rate for a mobile service or a service in a location having aweaker signal, such as an indoor location. Most particularly, thepresent invention may gain more enhanced robustness while ensuringcommonality with the conventional broadcasting/communication system.

By using a MIMO system, the present invention may increase datatransmission efficiency and may enhance robustness in broadcastingsignal transmission/reception.

Therefore, according to the present invention, the present invention mayprovide a method and device for transmitting/receiving a broadcastingsignal that can receive a digital broadcasting signal without any erroreven in a mobile receiving equipment or an indoor environment.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 illustrates an exemplary super frame structure according to thepresent invention,

FIG. 2 illustrates an exemplary structure of a signal frame according toan embodiment of the present invention,

FIG. 3 illustrates a PLP-based signal frame structure according to anembodiment of the present invention,

(a) of FIG. 4 illustrates a P1 symbol structure according to the presentinvention,

(b) of FIG. 4 illustrates a block diagram showing an exemplary structureof a P1 symbol generator according to the present invention,

FIG. 5 illustrates an exemplary structure of a P1 symbol and anexemplary structure of an AP1 symbol according to an embodiment of thepresent invention,

FIG. 6 illustrates a block diagram showing a broadcasting signaltransmitting apparatus according to an embodiment of the presentinvention,

FIG. 7 illustrates a block diagram showing an input pre-processoraccording to an embodiment of the present invention,

(a) and (b) of FIG. 8 illustrate an example of configuring a PLP incomponent units in an input pre-processor according to the presentinvention,

(a) and (b) of FIG. 9 illustrate another example of configuring a PLP incomponent units in an input pre-processor according to the presentinvention,

FIG. 10 illustrates a flow chart showing a pre-processing method of abroadcasting signal according to an embodiment of the present invention,

FIG. 11 illustrates a block diagram showing an input pre-processoraccording to another embodiment of the present invention,

(a) and (b) of FIG. 12 illustrate another example of configuring a PLPin component units in an input pre-processor according to the presentinvention,

FIG. 13 illustrates a flow chart showing a pre-processing method of abroadcasting signal according to another embodiment of the presentinvention,

FIG. 14 illustrates a block diagram showing an input processor accordingto an embodiment of the present invention,

FIG. 15 illustrates a block diagram showing a mode adaptation module ofan input processor according to an embodiment of the present invention,

FIG. 16 illustrates a block diagram showing a stream adaptation moduleof an input processor according to an embodiment of the presentinvention,

FIG. 17 illustrates a block diagram showing a BICM module according toan embodiment of the present invention,

FIG. 18 illustrates a block diagram showing a frame builder according toan embodiment of the present invention,

FIG. 19 illustrates a block diagram showing an OFDM generator accordingto an embodiment of the present invention,

(a) to (e) of FIG. 20 illustrate exemplary output orders of the bit-celldemux in accordance to each code rate, when an LDPC block length isequal to 16800, and when the modulation format that is to be used forsymbol mapping correspond to 256QAM,

FIG. 21 illustrates exemplary mapping correlation between the input bitsand the output bits of the bit-cell demux according demux type of FIG.20,

(a) to (c) of FIG. 22 illustrate other exemplary output orders of thebit-cell demux in accordance to each code rate, when an LDPC blocklength is equal to 16800, and when the modulation format that is to beused for symbol mapping correspond to 256QAM,

FIG. 23 illustrates exemplary mapping correlation between the input bitsand the output bits of the bit-cell demux according demux type of FIG.22,

(a) to (c) of FIG. 24 illustrate other exemplary output orders of thebit-cell demux in accordance to each code rate, when an LDPC blocklength is equal to 16800, and when the modulation format that is to beused for symbol mapping correspond to 256QAM,

(a) to (e) of FIG. 25 illustrate exemplary output orders of the bit-celldemux in accordance to each code rate, when an LDPC block length isequal to 16800, and when the modulation format that is to be used forsymbol mapping correspond to 64QAM,

(a) and (b) of FIG. 26 illustrate exemplary output orders of thebit-cell demux in accordance to each code rate, when an LDPC blocklength is equal to 16800, and when the modulation format that is to beused for symbol mapping correspond to 16QAM,

FIG. 27 illustrates a block diagram showing a broadcasting signalreceiving apparatus according to an embodiment of the present invention,

FIG. 28 illustrates a block diagram showing an OFDM demodulatoraccording to an embodiment of the present invention,

FIG. 29 illustrates a block diagram showing a P1 symbol detectoraccording to an embodiment of the present invention,

FIG. 30 illustrates a block diagram showing an AP1 symbol detectoraccording to an embodiment of the present invention,

FIG. 31 illustrates a block diagram showing a frame demapper accordingto an embodiment of the present invention,

FIG. 32 illustrates a block diagram showing a BICM decoder according toan embodiment of the present invention,

FIG. 33 illustrates a block diagram showing an output processoraccording to an embodiment of the present invention,

FIG. 34 illustrates a block diagram showing an output processoraccording to another embodiment of the present invention,

FIG. 35 illustrates a block diagram showing a broadcasting signalreceiving apparatus according to another embodiment of the presentinvention,

FIG. 36 illustrates a block diagram showing a broadcasting signalreceiving apparatus according to another embodiment of the presentinvention,

FIG. 37 illustrates a block diagram showing the process of thebroadcasting signal receiver for receiving a PLP best fitting itspurpose according to an embodiment of the present invention,

FIG. 38 illustrates a MIMO transmission system and a broadcast signaltransmitting method using an SVC according to an embodiment of thepresent invention,

FIG. 39 illustrates a MIMO transmission system and a broadcast signaltransmitting method using an SVC according to other embodiment of thepresent invention,

FIG. 40 illustrates a MIMO transmission system and a broadcast signaltransmitting method using an SVC according to another embodiment of thepresent invention,

(a) to (c) of FIG. 41 illustrate a signal frame for transmitting data ofa base layer and an enhancement layer according to embodiments of thepresent invention,

FIG. 42 illustrates a block diagram showing a broadcasting signaltransmitting apparatus according to another embodiment of the presentinvention,

FIG. 43 illustrates a block diagram showing a broadcasting signalreceiving apparatus according to another embodiment of the presentinvention,

FIG. 44 illustrates an exemplary syntax structure of P1 signalinginformation according to an embodiment of the present invention,

FIG. 45 illustrates an exemplary syntax structure of AP1 signalinginformation according to an embodiment of the present invention,

FIG. 46 illustrates an exemplary syntax structure of L1-pre signalinginformation according to an embodiment of the present invention,

FIG. 47 illustrates an exemplary syntax structure of configurableL1-post signaling information according to an embodiment of the presentinvention,

FIG. 48 illustrates an exemplary syntax structure of dynamic L1-postsignaling information according to an embodiment of the presentinvention,

FIG. 49 illustrates a conceptual diagram of a correlation between aservice and a PLP group according to a first embodiment of the presentinvention,

FIG. 50 illustrates an exemplary syntax structure of a delivery systemdescriptor according to the first embodiment of the present invention,

FIG. 51 illustrates a flow chart showing the process steps of a servicescanning method of a receiver according to the first embodiment of thepresent invention,

FIG. 52 illustrates a conceptual diagram of a correlation between aservice and a PLP group according to a second embodiment of the presentinvention,

FIG. 53 illustrates an exemplary syntax structure of a component IDdescriptor according to the second embodiment of the present invention,

FIG. 54 illustrates a flow chart showing the process steps of a servicescanning method of a receiver according to the second embodiment of thepresent invention,

FIG. 55 illustrates a conceptual diagram of a correlation between aservice and a PLP group according to a third embodiment of the presentinvention,

FIG. 56 illustrates an exemplary syntax structure of a delivery systemdescriptor according to the third embodiment of the present invention,

FIG. 57 illustrates an exemplary syntax structure of a component IDdescriptor according to the third embodiment of the present invention,

FIG. 58 illustrates an exemplary PLP_PROFILE field according to thethird embodiment of the present invention,

FIG. 59 illustrates a flow chart showing the process steps of a servicescanning method of a receiver according to the third embodiment of thepresent invention,

FIG. 60 illustrates a conceptual diagram of a correlation between aservice and a PLP group according to a fourth embodiment of the presentinvention,

FIG. 61 illustrates an exemplary syntax structure of anIP/MAC_location_descriptor according to the fourth embodiment of thepresent invention,

FIG. 62 illustrates a flow chart showing the process steps of a servicescanning method of a receiver according to the fourth embodiment of thepresent invention, and

FIG. 63 illustrates a flow chart showing a method for receiving abroadcasting signal according to an embodiment of the present invention.

FIG. 64 illustrates a flowchart showing a method for transmittingbroadcast data according to an embodiment of the present invention.

FIG. 65 illustrates a flowchart showing a method for receiving broadcastdata according to an embodiment of the present invention.

FIG. 66 illustrates a structure of an apparatus for transmittingbroadcast signals for future broadcast services according to anembodiment of the present invention.

FIG. 67 illustrates an input formatting module according to anembodiment of the present invention.

FIG. 68 illustrates an input formatting module according to anotherembodiment of the present invention.

FIG. 69 illustrates an input formatting module according to anotherembodiment of the present invention.

FIG. 70 illustrates a coding & modulation module according to anembodiment of the present invention.

FIG. 71 illustrates a frame structure module according to an embodimentof the present invention.

FIG. 72 illustrates a waveform generation module according to anembodiment of the present invention.

FIG. 73 illustrates a structure of an apparatus for receiving broadcastsignals for future broadcast services according to an embodiment of thepresent invention.

FIG. 74 illustrates a synchronization & demodulation module according toan embodiment of the present invention.

FIG. 75 illustrates a frame parsing module according to an embodiment ofthe present invention.

FIG. 76 illustrates a demapping & decoding module according to anembodiment of the present invention.

FIG. 77 illustrates an output processor according to an embodiment ofthe present invention.

FIG. 78 illustrates an output processor according to another embodimentof the present invention.

FIG. 79 illustrates a coding & modulation module according to anotherembodiment of the present invention.

FIG. 80 illustrates a demapping & decoding module according to anotherembodiment of the present invention.

FIG. 81 is a table showing requirements of the broadcast signaltransmission/reception apparatus and method according to one embodimentof the present invention.

FIG. 82 illustrates a super-frame structure according to an embodimentof the present invention.

FIG. 83 illustrates a preamble insertion block according to anembodiment of the present invention.

FIG. 84 illustrates a preamble structure according to an embodiment ofthe present invention.

FIG. 85 illustrates a preamble detector according to an embodiment ofthe present invention.

FIG. 86 illustrates a correlation detector according to an embodiment ofthe present invention.

FIG. 87 shows graphs representing results obtained when the scramblingsequence according to an embodiment of the present invention is used.

FIG. 88 shows graphs representing results obtained when a scramblingsequence according to another embodiment of the present invention isused.

FIG. 89 shows graphs representing results obtained when a scramblingsequence according to another embodiment of the present invention isused.

FIG. 90 is a graph showing a result obtained when a scrambling sequenceaccording to another embodiment of the present invention is used.

FIG. 91 is a graph showing a result obtained when a scrambling sequenceaccording to another embodiment of the present invention is used.

FIG. 92 illustrates a signaling information interleaving procedureaccording to an embodiment of the present invention.

FIG. 93 illustrates a signaling information interleaving procedureaccording to another embodiment of the present invention.

FIG. 94 illustrates a signaling decoder according to an embodiment ofthe present invention.

FIG. 95 is a graph showing the performance of the signaling decoderaccording to an embodiment of the present invention.

FIG. 96 illustrates a preamble insertion block according to anotherembodiment of the present invention.

FIG. 97 illustrates a structure of signaling data in a preambleaccording to an embodiment of the present invention.

FIG. 98 illustrates a procedure of processing signaling data carried ona preamble according to one embodiment.

FIG. 99 illustrates a preamble structure repeated in the time domainaccording to one embodiment.

FIG. 100 illustrates a preamble detector and a correlation detectorincluded in the preamble detector according to an embodiment of thepresent invention.

FIG. 101 illustrates a preamble detector according to another embodimentof the present invention.

FIG. 102 illustrates a preamble detector and a signaling decoderincluded in the preamble detector according to an embodiment of thepresent invention.

FIG. 103 is a flowchart illustrating a method for transmitting broadcastsignals according to an embodiment of the present invention.

FIG. 104 is a flowchart illustrating a method for receiving broadcastsignals according to an embodiment of the present invention.

BEST MODE FOR CARRYING OUT THE PRESENT INVENTION

Reference will now be made in detail to the preferred embodiments of thepresent invention, examples of which are illustrated in the accompanyingdrawings. Wherever possible, the same reference numbers will be usedthroughout the drawings to refer to the same or like parts. And, thescope and spirit of the present invention will not be limited only tothe exemplary embodiments presented herein.

Although the terms used in the present invention are selected fromgenerally known and used terms, the detailed meanings of which aredescribed in relevant parts of the description herein. It should benoted that the terms used herein may vary depending upon the intentionsor general practice of anyone skilled in the art and also depending uponthe advent of a novel technology. Some of the terms mentioned in thedescription of the present invention have been selected by the applicantat his or her discretion, terms used herein. Furthermore, it is requiredthat the present invention is understood, not simply by the actual termsused but by the meaning of each term lying within.

The present invention relates to an apparatus and method fortransmitting and receiving an additional broadcast signal, while sharingan RF frequency band with related art broadcasting system, such as aconventional terrestrial broadcast system (or also referred to as a T2system), e.g., DVB-T2. In the present invention, the additionalbroadcast signal may correspond to an extension (or enhanced) broadcastsignal and/or a mobile broadcast signal.

In the description of the present invention, an additional broadcastsignal refers to as signal that is processed and transmitted inaccordance with a non-MIMO (Multi Input Multi Output) method or a MIMOmethod. Herein, a MISO (Multi Input Single Output) method, a SISO(Single Input Single Output) method, and so on, may correspond to thenon-MIMO method.

Hereinafter, 2 antennae may be given as an example of the multi antennaeof the MISO method or the MIMO for simplicity of the description of thepresent invention. And, such description of the present invention may beapplied to all types of systems using 2 or more antennae.

FIG. 1 illustrates an exemplary super frame structure including anadditional broadcast signal (e.g., mobile broadcast signal) according tothe present invention. A super frame may be configured of a plurality offrames, and the frames belonging to one super frame may be transmittedby using the same transmission method. The super frame according to theembodiment of the present invention may be configured of multiple T2frames (also referred to as a terrestrial broadcast frame) andadditional non-T2 frames for the additional broadcast signal. Herein, anon-T2 frame may include an FEF (Future Extension Frame) part beingprovided by the related art T2 system. The FEF part may not becontiguous and may be inserted in-between the T2 frames. The additionalbroadcast signal may be included in the T2 frame or FEF part, so as tobe transmitted.

When a mobile broadcast signal is transmitted through FET part, the FEFpart will be referred to as an NGH (Next Generation Handheld) frame.

At this point, 1 NGH frame may be transmitted for each N number of T2frames (i.e., NGH-T2 frame ratio=1/N or N:1), and the T2 frame and theNGH frame may be alternately transmitted (i.e., NGH-T2 frame ratio=1/2or 1:1). If the NGH-T2 frame ratio is equal to 1/N, the time consumed bythe receiver in order to receive an NGH frame after receiving a previousNGH frame is equivalent to the time corresponding to N number of T2frames.

Meanwhile, among the components configuring a broadcast service, thepresent invention may divide a video component to multiple videocomponents and may transmit the divided video components. For example, avideo component may be divided into a basic video component and anextension video component, and may then be transmitted accordingly.

According to an embodiment of the present invention, in order to enhancetransmission stability, the basic video component may be transmitted ina non-MIMO method, and the extension video component may be transmittedin an MIMO method in order to provide an enhanced throughput.

In the present invention, the basic video component will hereinafter bereferred to as a video component of a base layer, and the extensionvideo component will hereinafter be referred to as a video component ofan enhancement layer. Additionally, for simplicity of the description,in the present invention, the video component of the base layer will beused in combination with video data of the base layer (or data of thebase layer), and the video component of the enhancement layer will beused in combination with video data of the enhancement layer (or data ofthe enhancement layer).

According to an embodiment of the present invention, the presentinvention may encode video data by using an SVC (Scalable Video Coding)method, thereby dividing the encoded video data into video data of thebase layer (or base layer video data) and video data of the enhancementlayer (or enhancement layer video data). Herein, the SVC method ismerely exemplary. And, therefore, other arbitrary video coding methodshaving scalability may also be used herein.

The data of the base layer (or the base layer data) correspond to datafor images having basic picture quality. Herein, although the base layerdata are robust against the communication environment, the base layerdata have low picture quality. And, the data of the enhancement layer(or the enhancement layer data) correspond to additional data for imagesof higher picture quality and may, therefore, provide images having highpicture quality. However, the enhancement layer data are weak againstthe communication environment.

In the present invention, video data for terrestrial broadcasting may bedivided into base layer data and enhancement layer data, and video datafor mobile broadcasting may be divided into base layer data andenhancement layer data in order to flexibly respond to the mobilebroadcasting communication environment.

The receiver may decode only video layer of the base data (or base layervideo data), so as to provide an image having basic picture quality, orthe receiver may decode both the base layer video data and the videolayer of the enhancement data (or enhancement layer video data), so asto provide an image having a higher picture quality.

According to an embodiment of the present invention the enhancementlayer video data may be transmitted through an FEF, and the base layerdata may be transmitted through the T2 frame and/or FEF.

In the present invention, an audio component may include an audiocomponent of a base layer (or base layer audio component) for providingbasic sound quality, such as 2 channel or 2.1 channel, and an audiocomponent of an enhancement layer (or enhancement layer audio component)for providing additional sound quality, such as 5.1 channel orMPEG-Surround.

According to an embodiment of the present invention, a signal frame mayrefer to any one of a T2 frame, an FEF transmitting a mobilebroadcasting signal (i.e., NGH frame), a T2 frame transmitting baselayer video data, and an FEF transmitting enhancement layer video data.In the description of the present invention, the signal frame and thetransmission frame will be used to have the same meaning.

In the present invention, a PLP (physical layer pipe) corresponding toan identifiable data (or stream) unit. Also, the PLP may be consideredas a physical layer TDM (Time Division Multiplex) channel, whichtransmits (or delivers) one or more services. More specifically, eachservice may be transmitted and received through multiple RF channels.Herein, the PLP may represent a path through which such service is beingtransmitted or may represent a stream being transmitted through suchpath. The PLP may also be located in slots being distributed to multipleRF channels at predetermined time intervals, and the PLP may also bedistributed in a single RF channel at predetermined time intervals.Therefore, signal frame may transmit a PLP, which is distributed to asingle RF channel based upon a time reference. In other words, one PLPmay be distributed to a single RF channel or multiple RF channels basedupon a time reference.

In the present invention, one service may be transmitted to one PLP, andcomponents configuring a service may be divided (or differentiated), sothat each of the differentiated components can be transmitted to adifferent PLP. If service components configuring a single service aredifferentiated from one another so as to be respectively transmitted toa different PLP, the receiver may gather (or collect) the multiplecomponents, so as to combine the collected components to a singleservice. In the present invention, the service component and thecomponent will be used to have the same meaning.

FIG. 2 illustrates an exemplary structure of a signal frame over aphysical layer according to an embodiment of the present invention. Thesignal frame includes a P1 signaling information region (or part), an L1signaling information region, and a PLP region. More specifically, theP1 signaling information region may be allocated to a foremost portionof the corresponding signal frame, and, then, the L1 signalinginformation region and the PLP region may be sequentially allocatedafter the P1 signaling information region. In the description of thepresent invention, only the information being included in the L1signaling information region may be referred to as L1 signalinginformation, or signaling information being included in the P1 signalinginformation region and signaling information being included in the L1signaling information region may be collectively referred to as the L1signaling information.

As shown in FIG. 2, P1 signaling information that is being transmittedto the P1 signaling information region may be used for detecting asignal frame and may include information for identifying preambleitself.

Based upon the P1 signaling information, the subsequent L1 signalinginformation region is decoded, so as to acquire information on the PLPstructure and the signal frame configuration. More specifically, the L1signaling information includes L1-pre-signaling information andL1-post-signaling information. Herein, the L1-pre-signaling informationincludes information required by the receiver to receive and decodeL1-post-signaling information. And, the L1-post-signaling informationincludes parameters required by the receiver for accessing the PLP. TheL1-post-signaling information may then include ConfigurableL1-post-signaling information, Dynamic L1-post-signaling information,Extension L1-post-signaling information, and CRC information, and theL1-post-signaling information may further include L1 padding data. Inthe present invention, configurable L1-post signaling information hasthe same meaning as the L1-post configurable signaling information.Moreover, dynamic L1-post signaling information has the same meaning asthe L1-post dynamic signaling information

Meanwhile, in the signal frame, the PLP region is configured of at leastone common PLP and at least one data PLP.

A common PLP includes PSI/SI (Program and System Information/SignalingInformation).

Specifically, when a broadcast signal is a TS format, the common PLP mayinclude network information, such as an NIT (Network Information Table),or PLP information, and service information, such as an SDT (ServiceDescription Table), an EIT (Event Information Table) and a PMT (ProgramMap Table)/a PAT (Program Association Table). Based upon the intentionsof the system designer, service information, such as SDT and PMT/PAT,may be included in data PLP and may then be transmitted. The PATcorresponds to special information being transmitted by a packet havinga PID of ‘0’, and the PAT includes PID information of the PMT and PIDinformation of the NIT. The PMT includes a program identificationnumber, PID information of a TS packet to which individual bit streams,such as video, audio, and so on, are being transmitted, wherein theindividual bit streams configure a program or (service), and PIDinformation through which a PCR is being delivered. The NIT includesinformation of an actual transmission network (i.e., physical network).The EIT includes information on an event (or program or service) (e.g.,title, start time, and so on). The SDT includes information describing aservice, such as a service name or service provider.

When a broadcasting signal corresponds to an IP format, the common PLPmay include an IP information table, such as n INT (IP/MAC notificationtable). In the description of the present invention information beingincluded in the common PLP may be referred to as L2 signalinginformation.

More specifically, L1 signaling information includes informationrequired by the broadcasting signal receiver for processing a PLP withina signal frame, and the L2 signaling information includes informationthat can be commonly applied to multiple PLPs. Accordingly, thebroadcasting signal receiver may use P1 signaling information includedin a P1 signaling information region, so as to decode an L1 signalinginformation region, thereby acquiring information on the structure ofPLP included in the signal frame and information a frame structure. Mostparticularly, the broadcasting signal receiver may be capable of knowingthrough which PLP each of the service components being included in thecorresponding service is being transmitted by referring to the L1signaling information and/or the L2 signaling information. Additionally,the BICM module of the broadcasting signal transmitter may encodesignaling information associated with a broadcast service and maytransmit L1/L2 signaling information, so that the broadcasting signalreceiver can perform decoding. Moreover, the MICM decoder of thebroadcasting signal receiver may decode the L1/L2 signaling information.

At this point, when the L1 signaling information includes information onthe service components, the broadcasting signal receiver may recognizethe information on the service components at the same time thebroadcasting signal receiver receives the signal frame, and thebroadcasting signal receiver may then apply the correspondinginformation. However, since the size of the L1 signaling information islimited, the size (or amount) of the information on the servicecomponents that can be transmitted from the broadcasting signaltransmitter may also be limited. Accordingly, the L1 signalinginformation region is most adequate for recognizing the information onthe service components at the same time the broadcasting signal receiverreceives the signal frame and for transmitting information that can beapplied to the broadcasting signal receiver.

If the L2 signaling information includes information on the servicecomponents, the broadcasting signal receiver may acquire information onthe service components after the decoding of the L2 signalinginformation is completed. Therefore, the broadcasting signal receivermay not be capable of recognizing the information on the servicecomponents at the same time the broadcasting signal receiver receivesthe signal frame and may not be capable of modifying the correspondinginformation. However, since the size of the region transmitting the L2signaling information is larger than the L1 signaling informationregion, the L2 signaling information region may transmit a larger amount(or size) of service component data. Accordingly, the L2 signalinginformation is adequate for transmitting general information on servicecomponents.

According to an embodiment of the present invention the L1 signalinginformation may be used along with the L2 signaling information. Morespecifically, the L1 signaling information may include information thatcan be modified (or changed) at the same time the broadcasting signalreceiver receives the signal frame in a PLP level, such as a high mobileperformance and a high-speed data communication characteristic, or mayinclude information of service components that can be modified (orchanged) at any time during the broadcasting signal transmission.Additionally, the L2 signaling information may include information onthe service components and general information on channel reception,which are included in a service.

Meanwhile, a data PLP, which is included in the signal frame, mayinclude audio, video, and data TS streams and PSI/SI information, suchas a PAT (Program Association Table), a PMT (Program Map Table). Thedata PLP may include a Type1 data PLP, which is transmitted by onesub-slice for each signal frame, and a Type2 data PLP, which istransmitted by multiple sub-slices. In the description of the presentinvention, for simplicity of the description, P number of data PLPs willhereinafter be indicated as PLP1˜PLPp. More specifically, audio, video,and data TS streams and PSI/SI information, such as PAT/PMT, aretransmitted through PLP1˜PLPp. The data PLPs of FIG. 2 correspond toexamples after scheduling and interleaving.

In the present invention the common PLP may be decoded along with a dataPLP, and the data PLP may be selectively (or optionally) decoded. Morespecifically, a common PLP+data PLP may always be decoded. However, insome cases data PLP1+data PLP2 may not be decoded. Information beingincluded in the common PLP may include the PSI/SI information.Additionally, Auxiliary Data may be added to the signal frame.

FIG. 3 illustrates a signal frame structure at a symbol level accordingto an embodiment of the present invention.

In light of the symbol level, the signal frame according to the presentinvention is divided intro a preamble region and a data region. Thepreamble region is configured of a P1 symbol and at least one or more P2symbols, and the data region is configured of a plurality of datasymbols.

Herein, the P1 symbol transmits P1 signaling information. The at leastone or more P2 symbols transmit L1-pre-signaling information,L1-post-signaling information, and signaling information being includedin the common PLP (i.e., L2 signaling information). The signalinginformation being included in the common PLP may be transmitted througha data symbol. Therefore, in light of the signal frame over a physicallayer, the preamble region includes a P1 signaling information region,an L1 signaling information region, and a portion or an entire portionof the common PLP region. In the description of the present invention aPLP transmitting PSI/SI and, more particularly, PAT/PMT will hereinafterbe referred to a base PLP.

Data PLPs being transmitted through multiple data symbols may include aType1 data PLP being transmitted, which is transmitted by one sub-slicefor each signal frame, and a Type2 data PLP, which is transmitted bymultiple sub-slices. According to an embodiment of the presentinvention, when both the Type 1 data PLP and the Type2 data PLP exist ina signal frame, the Type1 data PLP is first allocated, and the Type2data PLP is allocated afterwards.

The Type1 data PLP refers to having one sub-slice within a signal frame,i.e., one PLP being continuously transmitted within a signal frame. Forexample, when it is assumed that 2 type1 data PLPs (PLP1, PLP2) arebeing transmitted, when all of the data of PLP1 are first allocated tothe corresponding signal frame, then all of the data of PLP2 areallocated afterwards, and, thereafter, the data are transmitted.

The Type2 data PLP refers to a PLP having two or more sub-slices withinthe signal frame. More specifically, the data of each PLP are dividedinto as many sections as the number of sub-slices. And, then, thedivided data are distributed and transmitted to each sub-slice. Forexample, when it is assumed that 2 Type2 data PLP (PLP3, PLP4) exist ina single signal frame, and when it is assumed that each Type2 data PLPhas 2 sub-slices, the data of PLP3 and the data of PLP4 are each dividedinto 2 equal sections, and the divided data are sequentially allocatedto the 2 sub-slices of the corresponding PLP. At this point, accordingto the embodiment of the present invention, the sub-slice for PLP3 andthe sub-slice for PLP4 are alternately positioned so as to betransmitted accordingly. In order to gain higher time diversity, thepresent invention uses the Type2 data PLP.

In the description of the present invention, one data PLP may correspondto one service, and one data PLP may also correspond to any one of theservice components configuring a service, such as a video component (oralso referred to as a base layer video component), an extension videocomponent (or also referred to as an enhancement layer video component),and audio component, and a data component other than the video and audiocomponents.

Meanwhile, the present invention may transmit separate signalinginformation from the transmitter, so that the receiver can identifyadditional broadcast signal frame, such as an NGH frame, and process theidentified frame. The present invention transmits separate signalinginformation through a P1 symbol. And, herein, the P1 symbol will bereferred to as a new_system_P1 symbol.

The new_system_P1 symbol may be different from the P1 symbol, and aplurality of new_system_P1 symbols may be used herein. At this point,according to the embodiment of the present invention, the new_system_P1symbol is located at the beginning of the signal frame, i.e., located ata front portion of a first P2 symbol within a preamble region. In thiscase, the preamble region may be configured of at least one or morenew_system_P1 symbols and at least one or more P2 symbols.

(a) of FIG. 4 illustrates a P1 symbol structure according to the presentinvention. In (a) of FIG. 4, the P1 symbol and P2 symbol portion will bereferred to as a preamble region, and a body region will be referred toas a data region. The data region may be configured of a plurality ofdata symbols (also referred to as data OFDM symbols).

In (a) of FIG. 4, P1 symbol is generated by having each of a frontportion and an end portion of an effective (or valid) symbol copied, byhaving a frequency shift performed as much as +f_(sh), and by having thefrequency-shifted copies respectively positioned at a front portion (C)and an end portion (B) of the effective symbol (A). In the presentinvention, the C portion will be referred to as a prefix, and the Bportion will be referred to as a postfix. More specifically, P1 symbolis configured of a prefix portion, an effective symbol portion, and apostfix portion. In the description of the present invention, such P1symbol structure will also be referred to as a C-A-B structure. At thispoint, according to the present invention, the P1 symbol corresponds to1K OFDM symbol. And, according to the embodiment of the presentinvention, the A portion (T_(P1A)) may have the length of 112 us, the Cportion (T_(P1C)) may have the length of 59 us, and the B portion(T_(P1B)) may have the length of 53 us.

(b) of FIG. 4 illustrates a block diagram showing an exemplary structureof a P1 symbol generator according to the present invention. Herein, (b)of FIG. 4 includes a CDS (Carrier Distribution Sequence) table module(000100), an MSS (Modulation Signaling Sequence) module (000200), aDBPSK (Differential Binary Phase Shift Keying) mapping module (000300),a scrambling module (000400), a padding module (000500), an IFFT module(000600), and a C-A-B structure module (000700). After being processedwith the operations of each block included in the P1 symbol generatorshown in (b) of FIG. 4, the P1 symbols shown in (a) of FIG. 4 is finallyoutputted from the C-A-B structure module (000700).

According to the embodiment of the present invention, the structure ofthe P1 symbol, shown in (a) of FIG. 4, may be modified, or the P1 symbolgenerator, shown in (b) of FIG. 4 may be modified, so as to generate anew_system_P1 symbol.

If the new_system_P1 symbol is generated by modifying the P1 symbolshown in (a) of FIG. 4, the new_system_P1 symbol may be generated byusing at least one of the following methods. For example, thenew_system_P1 symbol may be generated by modifying a frequency shift (ordisplacement) value (f_(SH)) for a prefix and a postfix. In anotherexample, the new_system_P1 symbol may be generated by modifying (orchanging) the length of the P1 symbol (e.g., T_(P1C) and T_(P1B)lengths). In yet another example, the new_system_P1 symbol may begenerated by replacing the length of the P1 symbol from 1K to512,256,128, and so on. In this case, the parameters (e.g. f_(SH),T_(SH), T_(P1C), T_(P1B)) that are used in the P1 symbol structureshould be adequately corrected.

If the new_system_P1 symbol is generated by modifying the P1 symbolgenerator shown in (b) of FIG. 4, the new_system_P1 symbol may begenerated by using at least one of the following methods. For example,the new_system_P1 symbol may be generated by using a method of changingthe distribution of active carriers (e.g., a method of having the CDStable module (000100) use another CSS (Complementary Set of Sequence)),which are used for the P1 symbol, through the CDS table module (000100),the MSS module (000200), and the C-A-B structure module (000700). Inanother example, the new_system_P1 symbol may be generated by using amethod of changing a pattern for transmitting information to the P1symbol (e.g., a method of having the MSS module (000200) use anotherCSS), and so on.

Meanwhile, the present invention may additionally allocate a preamblesymbol to the preamble region within a signal frame, particularly an NGHframe. Hereinafter, the additional preamble signal will be referred toas an AP1 symbol (Additional Preamble symbol) for simplicity in thedescription of the present invention. In order to enhance the detectionperformance for detecting a mobile broadcast (i.e., NGH) signal, in aconsiderably low SNR condition or a time-selective fading condition, atleast one or more AP1 symbol is added to the signal frame.

At this point, according to the embodiment of the present invention, theAP1 symbol is located between a P1 symbol and a first P2 symbol withinthe preamble region of a signal frame. More specifically, the P1 symboland the AP1 symbol are consecutively transmitted. According to theembodiment of the present invention, if the P2 symbol is not transmittedto the signal frame, the AP1 symbol may be located between the P1 symboland the first data symbol within the preamble region of the signalframe. According to another embodiment of the present invention, the P1symbol and the AP1 symbol may be allocated to non-consecutive positionswithin a single signal frame, so as to be transmitted.

For example, when a signal frame includes an AP1 symbol, the preambleregion of the signal frame is configured of a P1 symbol, at least one ormore AP1 symbols, and at least one or more P2 symbols. And, the dataregion may be configured of a plurality of data symbols (or data OFDMsymbols).

As described in the embodiments for generating the new_system_P1 symbol,according to the embodiment of the present invention, the AP1 symbol maybe generated by modifying the structure of the P1 symbol, shown in (a)of FIG. 4, or by modifying the P1 symbol generator, shown in (b) of FIG.4. According to the embodiment of the present invention, the AP1 symbolmay be generated by modifying both the structure of the P1 symbol, shownin (a) of FIG. 4, and the P1 symbol generator, shown in (b) of FIG. 4.

As described in the embodiment of the present invention, when at least 2or more preamble symbols are used, the present invention is advantageousin that the present invention can be more robust against a burst fadingeffect, which may occur in a mobile fading environment, and that asignal detection performance can be enhanced.

FIG. 5 illustrates an exemplary structure of a P1 symbol and anexemplary structure of an AP1 symbol according to an embodiment of thepresent invention. FIG. 5 shows an example of generating an AP1 symbolby modifying the P1 symbol.

In FIG. 5, P1 symbol, which is shown on the left side, is generated byhaving each of a front portion and an end portion of an effective (orvalid) symbol copied, by having a frequency shift performed as much as+f_(sh), and by having the frequency-shifted copies respectivelypositioned at a front portion (C) and an end portion (B) of theeffective symbol (A). In the present invention, the C portion will bereferred to as a prefix, and the B portion will be referred to as apostfix. More specifically, P1 symbol is configured of a prefix portion,an effective symbol portion, and a postfix portion.

In FIG. 5, AP1 symbol, which is shown on the right side, is generated byhaving each of a front portion and an end portion of an effective (orvalid) symbol copied, by having a frequency shift performed as much as−f_(sh), and by having the frequency-shifted copies respectivelypositioned at a front portion (F) and an end portion (E) of theeffective symbol (D). In the present invention, the F portion will bereferred to as a prefix, and the E portion will be referred to as apostfix. More specifically, AP1 symbol is configured of a prefixportion, an effective symbol portion, and a postfix portion.

Herein, the two frequency-shift values +f_(sh), −f_(sh), which are usedin the P1 symbol and the AP1 symbol, may have the same absolute valueyet be given opposite signs. More specifically, the frequency-shift isperformed in opposite directions. And, the lengths C and F, which arecopied to the front portion of the effective symbol, may be set to havedifferent values. And, the lengths B and E, which are copied to the endportion of the effective symbol, may be set to have different values.Alternatively, the lengths C and F may be set to have different values,and the lengths B and E may be set to have the same value, or viceversa. According to another embodiment of the present invention, aneffective symbol length of the P1 symbol and an effective symbol lengthof the AP1 symbol may be differently determined. And, according to yetanother embodiment of the present invention, a CSS (Complementary SetSequence) may be used for tone selection and data scrambling within theAP1 may be scrambled by AP1.

According to the embodiment of the present invention, the lengths of Cand F, which are copied to the front portion of the effective (or valid)symbol, may be set to have different values, and the lengths of B and E,which are copied to the end portion of the effective (or valid) symbol,may also be set to have different values.

The C,B,F,E lengths according to the present invention may be obtainedby using Equation 1 shown below.Length of C(T _(C))={Length of A(T _(A))/2+30}Length of B(T _(B))={Length of A(T _(A))/2−30}Length of E(T _(F))={Length of D(T _(D))/2+15}Length of E(T _(E))={Length of D(T _(D))/2−15}  Equation 1

As shown in Equation 1, P1 symbol and AP1 symbol have the same frequencyshift value. However, each of the P1 symbol and the AP1 symbol are givenopposite signs. Additionally, in order to determine the lengths of C andB, the present invention determines an offset value being added to orsubtracted from a value corresponding to the length of A (T_(A))/2. And,in order to determine the lengths of F and E, the present inventiondetermines an offset value being added to or subtracted from a valuecorresponding to the length of D (T_(D))/2. Herein, each of the offsetvalues is set up differently. According to the embodiment of the presentinvention, the offset value of P1 symbol is set to 30, and the offsetvalue of AP1 symbol is set to 15. However, the values given in theabove-described examples are merely exemplary. And, therefore, it willbe apparent that the corresponding values may easily be varied orchanged by anyone skilled in the art. Thus, the present invention willnot be limited only to the values presented herein.

According to the present invention, by generating AP1 symbol and an AP1symbol to configure the structure shown in FIG. 5, and by inserting thegenerated symbols to each signal frame, the P1 symbol does not degradethe detection performance of the AP1 symbol, and, conversely, the AP1symbol does not degrade the detection performance of the P1 symbol.Additionally, the detection performance of the P1 symbol is almostidentical to the detection performance of the AP1 symbol. Furthermore,by configuring the symbols so that the P1 symbol and the AP1 symbol havesimilar symbol structures, the complexity level of the receiver may bereduced.

At this point, the P1 symbol and the AP1 symbol may be transmittedconsecutively, or each of the symbols may be allocated to differentpositions within the signal frame and may then be transmitted. And, incase the P1 symbol and AP1 symbol are each allocated to a differentposition within the signal frame, so as to be transmitted, a high timediversity effect may be gained with respect to the preamble symbol.According to the embodiment of the present invention, the P1 symbol andthe AP1 symbol are consecutively transmitted.

FIG. 6 illustrates a block diagram showing a broadcasting signaltransmitting device (or also referred to as a broadcasting signaltransmitter or a transmitter) according to an embodiment of the presentinvention.

As shown in FIG. 6, the broadcasting signal transmitting device mayinclude an input pre-processor (100000), an input processor (100100), aBICM module (100200), a frame builder (100300), and an OFDM generator(100400). Herein, the BICM module (100200) is also referred to as a BICMencoder.

The input stream may include at least one of a TS stream, an internetprotocol (IP) stream, and a GSE (General Stream Encapsulation) stream(or also referred to as a GS stream).

The input pre-processor (100000) may receive at least one the TS stream,the IP stream, and the GS stream, so as to generate at least one or morePLPs in service units (or service component units) in order to providerobustness.

The input processor (100100) generates a BB frame including at least oneor more of the PLPs generated from the input pre-processor (100000). Incase the input processor (100100) receives a PLP corresponding to aservice, the input processor (100100) may categorize the received PLP asPLPs corresponding to the service components and may, then, generate theBB frame.

The BICM module (100200) adds redundancy to the output of the inputprocessor (100100), so that any error occurring over the transmissionchannel can be corrected, and then the BICM module (100200) performsinterleaving.

The frame builder (100300) maps the plurality of PLPs to thetransmission frame is cell units, so as to complete the transmissionframe (or signal frame) structure.

The OFDM generator (100400) performs OFDM modulation on the input data,so as to generate a baseband signal that can be transmitted to theantenna.

As described above, according to an embodiment of the present invention,the input pre-processor (100000) may categorize the data correspondingto the service to each component, and, then, the input pre-processor(100000) may perform data processing, so that the data corresponding toeach component can be transmitted to a separate PLP.

The broadcasting signal transmitting device according to the presentinvention may be transmitted to one or more services in PLP units.However, the components being included in one service may be separatedand transmitted in PLP units. In this case, the broadcasting signalreceiving device may identify and process the PLPs including eachcomponent, so as to be capable of providing a single service. In orderto do so, the input pre-processor (100000) according to the presentinvention processes data in component units.

In the following description of the present invention, an example ofgenerating a PLP by receiving a stream having a TS format and an exampleof generating a PLP by receiving a stream having an IP format will beseparately described.

FIG. 7 illustrates a block diagram of the present invention showing astructure of the input pre-processor receiving a stream having a TSformat according to an embodiment of the present invention.

The input pre-processor of FIG. 7 includes a PID filter (101010), aPSI/SI controller (101020), a PSI/SI decoder (101030), a PSI/SImodifying/generating module (101040), a PSI/SI merger (101050), aPAT/PMT merger (101070), component mergers (101090, 101110), and nullpacket inserting modules (101060, 101080, 101100, 101120).

The input pre-processor differentiates the TS packets included in the TSfor each component, and outputs each of the differentiated TS packets toa different PLP. Herein, each TS packet is configured of a header and apayload, and the header includes a Packet Identifier (PID) indicatingthe data to which the header data correspond. The payload may includeany one of a video Elementary Stream (ES), an audio ES, a data ES, and aPSI/SI ES, which are to be transmitted. Additionally, informationincluded in the common PLP may also be referred to as L2 signalinginformation or L2 information/data, and L1 signaling information mayalso be referred to as L1 information.

According to an embodiment of the present invention, when the videocomponent is divided into a base layer video component and anenhancement layer video component, the PID of a TS packet including thebase layer video component and the PID of a TS packet including theenhancement layer video component are different from one another.

More specifically, the PID filter (101010) filters the TS packetsincluded in the TS by using the PID and then outputs the filtered TSpackets through a corresponding PLP path. Since each TS packet isassigned with a PID, which can identify each TS packet, the PID filter(101010) may identify the TS packets corresponding to each component byusing the PID and may then output the identified TS packets through aseparate PLP path. However, since the PID information should be known inorder to perform filtering as described above, the PID filter (101010)first filters the PSI/SI, which is included in the TS packet. The PSI/SIdecoder (101030) decodes the PSI/SI information, which is filtered bythe PID filter (101010), so as to acquire PID information. For example,a PAT having the PID fixed to ‘0’ includes PID information of the PMTand PID information of the NIT, and the PMT includes PID information,such as video, audio, data ES, and so on, corresponding to eachcomponent.

Additionally, the PSI/SI controller (101020) may use the acquired PIDinformation so as to control the PID filter (101010), thereby filteringthe data corresponding to the wanted (or desired) component for each PIDand outputting the filtered data. Since the PSI/SI included in the TSare transmitted by using a predetermined PID, the filtering and dataprocessing procedures may be performed without setting up a separate PIDfilter (101010).

As described above, the PID filter (101010) filters the TS packet foreach component and outputs each of the filtered TS packets through itsrespective PLP path. For example, a TS corresponding to the videocomponent, a TS corresponding to the audio component, and a TScorresponding to the data component are each outputted to the respectivecomponent merger (101090, 101110). And, the component mergers (101090,101110) merge the inputted TS packets so as to configure each componentPLP. For example, the component merger (101090) may receive only the TSpackets corresponding to a base layer video component, or may receiveboth the TS packets corresponding to a base layer video component andthe TS packets corresponding to an enhancement layer video component.Then, the component merger (101090) may merge the received TS packets,so as to configure a single component PLP. Furthermore, TS packetsincluding the PAT/PMT being filtered by and outputted from the PIDfilter (101010) are outputted to the PAT/PMT merger (101070), so as tobe merged.

Thus, when configuring the PLP for each component as described above,even if the receiver scans a channel, the receiver may not be capable ofsearching all of the data corresponding to a single service. Morespecifically, unlike the method of configuring a PLP for each serviceand identifying the configured PLP by using the PSI/SI, since the PLP isconfigured for each component configuring a service in the presentinvention, a component PLP that does not include PSI/SI may exist.Accordingly, in the present invention, in order to locate component PLPsconfiguring a service, PSI/SI, such as a PAT/PMT is added to anarbitrary PLP among the component PLPs configuring the correspondingservice, and a component PLP having service configuration information,such as the above-mentioned PAT/PMT will hereinafter be referred to as abase PLP. When the receiver scans and decodes the base PLP, sinceinformation on the remaining component PLPs for providing a service maybe known, the above-described problem may be resolved.

The PSI/SI modifying/generating module (101040) modifies or generatesPSI/SI that is to be modified or added, such as NIT, SDT, and so on, andthen outputs the modified or generated PSI/SI. For example, in theabove-described component PLP structure, since the base PLP includesinformation on the service configuration, such information on theservice configuration or information on the base PLP is required to besignaled. The input pre-processor may signal the information on the basePLP to at least any one of L1 signaling information and L2 signalinginformation (common PLP). When signaling the information on the base PLPto the L2 signaling information, the PSI/SI modifying/generating module(101040) may signal the information on the base PLP to an NIT/SDT_otheror a PAT/PMT. The information on the base PLP may include informationfor searching the base PLP, information required for extracting the basePLP and decoding the extracted base PLP, information on a PAT/PMTrespective to the service configuration included in the base PLP.Additionally, according to the embodiment of the present invention,information on components for a service having high picture quality/highsound quality, such as SVC, MPEG surround, and so on, is signaled to theL1 signaling information.

The SDT may be indicated as SDT_actual and SDT_other, and the EIT may beindicated as EIT_actual and EIT_other. Herein, the SDT_actual/EIT_actualmay each indicate that the service/event indicated by the respectiveinformation corresponds to service/event included in the current frameor TS, and the SDT_other/EIT_other may each indicate that theservice/event corresponds to service/event included in another frame orTS. In case the PSI/SI extracted from the TS includes a common PLP, thePSI/SI modifying/generating module (101040) may also modify theSDT_actual to an SDT_other or may modify the EIT_actual to an EIT_other.

The PSI/SI merger (101050) merges the signaling information beingoutputted from the PSI/SI modifying/generating module (101040) and thesignaling information being outputted from the PID filter (101010).

The null packet inserting modules (101060, 101080, 101100, 101120)respectively insert a null packet to a place (or positions) whereanother component has been located, so that each component can maintainsynchronization within the TS. Accordingly, a common PLP is outputtedfrom null packet inserting module (101060), and a base PLP is outputtedfrom null packet inserting module (101080). Additionally, thecorresponding component PLPs are outputted from null packet insertingmodules (101100, 101120). Herein, the respective component maycorrespond to a video component, an audio component, a data component,and so on.

As shown in FIG. 7, the input pre-processor may receive a TS and mayoutput data including the PSI/SI through a common PLP path, may outputdata corresponding to a component PLP, which includes serviceconfiguration information, through a base PLP path, and may output datacorresponding each of the other components through a correspondingcomponent PLP path, and the data corresponding to each of theabove-mentioned PLP path may also be referred to as PLP data or PLP.

The input pre-processor may signal the information on the components,which are configured as described above, to the L1 signalinginformation, so that components can be extracted in PLP units inaccordance with the receiver type. In other words, when a service typeis selected in accordance with the receiver, the receiver shall processthe components corresponding to the selected service. In the presentinvention, since the PLP is configured for each component, informationon such PLP structure should be included in the L1 signalinginformation, so that the receiver can extract and process the componentscorresponding to the service. Therefore, the input pre-processor mayperform control operations enabling information on the component PLPstructure to be signaled to the L1 signaling information.

(a) and (b) of FIG. 8 illustrate a example of configuring a PLP incomponent units in an input pre-processor according to the presentinvention.

In (a) of FIG. 8, the TS (102010) being configured of TS packetsindicate a TS being inputted to the input-pre-processor of FIG. 7. And,each TS packet includes one of data corresponding to an audio component,data corresponding to a video component, data corresponding to a datacomponent, and data corresponding to a PSI/SI component.

The input pre-processor of FIG. 7 performs the above-describedpre-processing procedure on the TS packets included in the TS stream(102010), so as to differentiate the TS packets for each component,thereby outputting each of the differentiated TS packets to a differentPLP path.

For example, as shown in (b) of FIG. 8, TS packets including NIT, SDT,EIT are outputted through a common PLP path, thereby configuring acommon TS (102020), and TS packets including data of the video componentare outputted through a video component PLP path, thereby configuring avideo component TS (102030). Additionally, the TS packets including dataof the audio component are outputted through an audio component PLPpath, thereby configuring an audio component TS (102040), and the TSpackets including data of the data component and PAT/PMT information areoutputted through a data component PLP path, thereby configuring a datacomponent TS (102050). In another example, TS packets including data of2 or more components may be outputted through a single PLP path, so asto configure a single TS. In yet another example, TS packets includingdata of a specific component respective to multiple services may beoutputted through a single PLP path, so as to configure a single TS.

Also, when the input pre-processor separates TS packets, each beingconfigured a different component, such as audio, video, data, and so on,to each component, in order to maintain synchronization among eachcomponent, the input pre-processor may insert a null packet in theposition of another component in each component TS.

For example, the common TS (102020) inserts a null packet in a positionof a TS packet (or TS packet position) including audio, video, Data,PAT, PMT, and the video component TS (102030) inserts a null packet in aposition of a TS packet (or TS packet position) including audio, NIT,SDT, EIT, Data, PAT, PMT. Moreover, the audio component TS (102040)inserts a null packet in a position of a TS packet (or TS packetposition) including video, NIT, SDT, EIT, Data, PAT, PMT, and the datacomponent TS (102050) inserts a null packet in a position of a TS packet(or TS packet position) including audio, video, NIT, SDT, EIT. Theinsertion of the null packet is performed by the null packet insertingmodules (101060, 101080, 101100, 101120) of FIG. 7. Each of the TSs ofeach component, having a null packet included therein, is outputted tothe input processor (100100).

For simplicity in the description of the present invention, the commonTS (102020) having a null packet inserted therein may also be referredto as a common PLP (or PLP data), and the video component TS (102030)having a null packet inserted therein may also be referred to as a videocomponent PLP (or PLP data). Additionally, the audio component TS(102040) having a null packet inserted therein may also be referred toas an audio PLP (or PLP data), and the data component TS (102050) havinga null packet inserted therein may also be referred to as a datacomponent PLP (or PLP data).

(a) and (b) of FIG. 9 illustrate another example of configuring a PLP incomponent units in an input pre-processor according to the presentinvention.

(a) of FIG. 9 shows an example of TSs being outputted for each componentfrom the input pre-processor (100000), and (b) of FIG. 9 shows anexample of TSs being outputted for each component from the inputprocessor (100100).

The input processor (100100) deletes null packets other than the validpackets from each TS being outputted from the input pre-processor(100000). And, then, the input processor (100100) inserts information ona number of Deleted null packet (DNP) in accordance with the deletedpositions. More specifically, the null packets other than the validpackets are reduced to DNP bytes in each TS.

Referring to each component PLP in (b) of FIG. 9, it will be apparentthat a null packet is deleted from each TS, and that a DNP byteindicating the number of deleted null packets are inserted instead.Additionally, it will also be apparent that a synchronization byte formatching the synchronization in the receiving end is inserted beforeeach DNP byte.

For simplicity in the description of the present invention, as shown in(b) of FIG. 9, a common TS having a null packet deleted therefrom andhaving a DNP byte inserted therein may also be referred to as a commonPLP (or PLP data), and a video component TS having a null packet deletedtherefrom and having a DNP byte inserted therein may also be referred toas a video component PLP (or PLP data). Additionally, an audio componentTS having a null packet deleted therefrom and having a DNP byte insertedtherein may also be referred to as an audio component PLP (or PLP data),and a data component TS having a null packet deleted therefrom andhaving a DNP byte inserted therein may also be referred to as a datacomponent PLP (or PLP data).

FIG. 10 illustrates a flow chart showing a pre-processing method of abroadcasting signal according to an embodiment of the present invention.

FIG. 10 shows an exemplary method of having the input pre-processor(100000) of FIG. 7 separate (or divide) the TS in component units andhaving the input pre-processor (100000) output data of the separatedcomponent unit to each separate PLP path.

The input pre-processor (100000) uses the PID filter (101010), so as tofilter the TS packets including PAT/PMT from an input TS (S105010).Since the PAT/PMT is transmitted as a static PID from the correspondingTS packet, filtering may be performed without any separate PID filtersettings. Also, the PID of the PMT may be acquired from the PAT.

The input pre-processor (100000) uses the PSI/SI decoder (101030), so asto decode the filtered PAT/PMT, thereby acquiring PID information oneach component (S105020). Moreover, the PSI/SI controller (101020) setsup the PID filter (101010) by using the decoded PID information, so asto filter the TS packets for each component, thereby outputting thefiltered TS packets (S105030).

The input pre-processor (100000) may perform other operations inaccordance with the component type (S105040).

When the component type corresponds to the PSI/SI, i.e., when thecomponent type corresponds to common PLP data, the input pre-processor(100000) determines whether or not the PSI/SI requires to be modified(S105050). And, when modification is required, the corresponding PSI/SIis generated or modified (S105050). Additionally, the inputpre-processor (100000) may use the PSI/SI modifying/generating module(101040), so as to signal information on a base PLP to the NIT/SDT_otheror PAT/PMT as described above in the description of FIG. 7, and tomodify NIT, SDT, EIT information. Moreover, the input pre-processor(100000) may use the PSI/SI merger (101050), so as to merge signalinginformation that should be included in the PSI/SI component (S105070).

When the component type does not correspond to the PSI/SI, i.e., whenthe component type corresponds to component PLP data, the inputpre-processor (100000) determines whether or not the data corresponds toa base PLP among the component PLPs (S105100). In case of the datarespective to the base PLP, the input pre-processor (100000) merges thePAT/PMT with the data included in the base PLP, and such information onthe base PLP is signaled to the L2 signaling information. In this step,the L2 signaling information may be determined to signal information onthe base PLP to the NIT/SDT_other or PAT/PMT, and the PAT/PMT may bedetermined to signal service configuration information respective to thecomponent structure. And, this may be performed along with theabove-described step (S105060).

The input pre-processor (100000) uses the PAT/PMT merger (101070), so asto merge the PAT/PMT including the service configuration information tothe base PLP data (S105120). Additionally, the input pre-processor(100000) may determine a physical PLP parameter based upon the componenttype, so that the physical PLP parameter can be signaled to the L1signaling information (S105130). In other words, the input pre-processor(100000) may signal information on the component PLP structure to the L1signaling information, so that the receiver can process the componentPLP corresponding to the service.

The input pre-processor (100000) inserts a null packet in PLP data,which are processed in accordance with the component type (S105080). Thenull packet insertion procedure is identical to the procedure describedwith reference to FIG. 7 and FIG. 8. Each set of component PLP datahaving the null packet inserted therein is outputted to a respective PLPpath (S105090).

Hereinafter, the input pre-processor processing data having an IP streamformat will hereinafter be described in detail.

In case of an IP stream, unlike the description presented above, thedata corresponding to the component may be divided in IP packet units.And, the PSI/SI included in the TS may correspond to serviceinformation, and the IP service information may include ESG (ElectronicService Guide; ESG) information, provider information, bootstrapinformation, and so on. The ESG information may include IP addressinformation, port number information, and so on of the servicecomponent. According to the embodiment of the present invention, the IPstream may be inputted/outputted in GSE (Generic Stream Encapsulation)stream units.

FIG. 11 illustrates a block diagram showing the structure of an inputpre-processor receiving a stream having an IP format according to anembodiment of the present invention.

The input pre-processor (100000) of FIG. 11 includes a UDP/IP filter(106010), an IP service controller (106020), an IP service informationdecoder (106030), an IP service information modifying/generating module(106040), an IP stream merger (106050), GSE encapsulating modules(106060, 106080, 106100, 106120), component mergers (106070, 106090,106110), and a GSE decapsulating module (106130).

The input pre-processor (100000) of FIG. 11 receives a GSE stream or IPstream and differentiates the data included in the received stream foreach component, thereby outputting the differentiated data to adifferent PLP. At this point, a PLP including IP service information maybe referred to as a common PLP, and the common PLP may also be referredto as L2 signaling information or L2 information/data. The L1 signalinginformation may also be referred to as L1 information.

In the present invention, the GSE stream is inputted to the GSEdecapsulation module (106130), and the IP stream is inputted to theUDP/IP filter (106010). The GSE decapsulation module (106130) performsGSE decapsulation on the GSE stream, so as to extract an IP stream,thereby outputting the extracted IP stream to the UDP/IP filter(106010).

The UDP/IP filter (106010) may use a UDP port number and an IP address,and so on, so as to perform filtering on the IP packets, which areincluded in the IP stream, for each component, thereby outputting thefiltered IP packets. Since a UDP port number and an IP address areassigned (or allocated) to each of the IP packets for each component,which are included in the IP stream, the UDP/IP filter (106010) may usethe UDP port number and IP address so as to identify the IP packetcorresponding to each component, thereby outputting each of theidentified IP packets to a separate PLP path. Hereinafter, such UDP portnumber and IP address may also be collectively referred to as an addressor address information.

However, since a UDP port number and an IP address should be known inorder to perform such filtering process, the UDP/IP filter (106010)first filters the IP service information included in the IP stream.Then, the IP service information decoder (106030) decodes the IP serviceinformation, which is filtered by the UDP/IP filter (106010), so as toacquire address information. At this point, the address information maybe acquired from the ESG information among the IP service information.Additionally, the IP service controller (106020) may use the addressinformation, which is acquired from the IP service information decoder(106030), so as to control the UDP/IP filter (106010) and to filter theIP packet corresponding to a desired component for each address, therebyoutputting the filtered IP packet. Since the IP service information,which is included in the IP stream, is transmitted to a predeterminedaddress, an immediate filtering process may be performed without anyseparate settings of the UDP/IP filter (106010).

The UDP/IP filter (106010) first filters the IP packets included in theIP stream for each component and then outputs the filters IP packets toa respective component merger through each PLP path. For example, IPpackets corresponding to the video component are outputted to thecomponent merger (106070), IP packets corresponding to the audiocomponent are outputted to the component merger (106090), and IP packetscorresponding to the data component are outputted to the componentmerger (106110). The component mergers (106070, 106090, 106110) mergethe IP packets of the corresponding component. If the stream beinginputted to the input pre-processor corresponds to a stream having a GSEformat, the output of the component mergers (106070, 106090, 106110) isoutputted as a GSE stream, after being GSE encapsulated by each GSEencapsulating module. And, if the corresponding stream has an IP format,the GSE encapsulating process may be omitted.

When configuring the PLP for each component as described above, thereceiver may not be capable of searching all of the data correspondingto a single service, even when the channel is scanned. Morespecifically, unlike the method of configuring a PLP for each serviceand identifying the configured PLP as IP service information, since thePLP is configured for each component configuring a service, a componentPLP that does not include any IP service information may exist in thepresent invention. Therefore, in the present invention, serviceconfiguration information is added to the IP service information so thatthe component PLPs corresponding to a service can be located and found.

The IP service information modifying/generating module (106040) maymodify or generate IP service information that should be modified oradded, such as ESG information, service provider information, bootstrapinformation, and so on and may, then, output the modified or generatedIP service information. For example, service configuration informationconfiguring a PLP for each component may be signaled to the ESGinformation.

The IP stream merger (106050) merges IP service informationmodified/generated by the IP service information modifying/generatingmodule (106040) and IP service information, such as supplementalinformation, which does not require any modification, thereby outputtingthe merged IP service information to a common PLP path.

According to the embodiment of the present invention, since an IPaddress and a UDP port number are each assigned (or allocated) in IPpacket units to the IP stream, the null packet inserting modules shownin FIG. 7 may be omitted.

As shown in FIG. 11, the input pre-processor may receive an IP stream(or GSE stream) and may output data including IP service information toa common PLP path and may output data corresponding to each component toa component PLP path. Accordingly, as described above, the datacorresponding to each PLP path may also be referred to as PLP data orPLP.

The input pre-processor may signal information on the components, whichare configured as described above, to the L1 signaling information, sothat components can be extracted in PLP units in accordance with thereceiver type. More specifically, when a service type is selected inaccordance with the receiver, the receiver shall process the componentscorresponding to the selected service. In the present invention, since aPLP is configured for each component, the information on such PLPconfiguration is signaled to the L1 signaling information, therebyallowing the receiver to extract the components corresponding to theselected service and to process the extracted components. Accordingly,the input pre-processor may generate information on the PLPconfiguration, so as to perform control operations enabling thegenerated information to be included in the L1 signaling information.

FIG. 12 illustrates an example of configuring a PLP in component unitsin an input pre-processor according to another embodiment of the presentinvention.

In FIG. 12, an IP stream (107010) being configured of IP packetsindicates an IP stream being inputted to the UDP/IP filter (106010) ofthe input pre-processor shown in FIG. 11. And, each IP packet includesone of audio component data, video component data, data component data,and IP service information component data.

The input pre-processor of FIG. 12 performs the above-describedpre-processing procedure on the IP packets included in the IP stream(107010), so as to differentiate the pre-processed IP packets for eachcomponent, thereby outputting each of the differentiated IP packetsthrough a different PLP path.

For example, IP packets including NIT, INT, bootstrap, ESG informationare outputted through a common PLP path, thereby configuring a common IP(107020), and IP packets including data of the video component areoutputted through a video component PLP path, thereby configuring avideo component IP (107030). Additionally, the IP packets including dataof the audio component are outputted through an audio component PLPpath, thereby configuring an audio component IP (107040), and the IPpackets including data of the data component are outputted through adata component PLP path, thereby configuring a data component IP(107050). In another example, IP packets including data of 2 or morecomponents may be outputted through a single PLP path, so as toconfigure a single IP. In yet another example, IP packets including dataof a specific component respective to multiple services may be outputtedthrough a single PLP path, so as to configure a single IP.

For simplicity in the description of the present invention, a common IPstream (107020) may be referred to as a common PLP (or PLP data), and avideo component IP stream (107030) may be referred to as a videocomponent PLP (or PLP data). Additionally, an audio component IP stream(107040) may be referred to as an audio component PLP (or PLP data), anda data component IP stream (107050) may be referred to as a datacomponent PLP (or PLP data).

Based upon the characteristics of the IP streams, the IP streams of eachPLP path of FIG. 12 are not required to maintain the samesynchronization or order.

FIG. 13 illustrates a flow chart showing a pre-processing method of abroadcasting signal according to another embodiment of the presentinvention.

FIG. 13 shows a processing method of the above-described inputpre-processor (100000) of FIG. 11, so that an IP stream can be dividedin component units, and so that each set of component unit data can beoutputted to a different PLP path.

In case the input stream corresponds to a GSE stream, the inputpre-processor (100000) may use the GSE decapsulating module (106130), soas to decapsulate the GSE stream to an IP stream (S109010). In case theinput stream corresponds to an IP stream, this process step (S109010)may be omitted.

The input pre-processor (100000) may use the UDP/IP filter (106010), soas to filter the ESG information of the input IP stream (S109020). Sincethe ESG information is transmitted from an IP stream to a predeterminedaddress, a filtering procedure may be performed without any separatefilter set-up.

The input pre-processor (100000) may use the IP service informationdecoder (106030), so as to decode the ESG information, which is filteredby the UDP/IP filter (106010) and to acquire address informationrespective to each component included in the IP stream (S109030).Thereafter, the IP service controller (106020) may set up the UDP/IPfilter (106010) by using the address information, which is acquired instep (S109030), so as to filter data for each component and to outputthe filtered data (S109040).

The input pre-processor (100000) performs another operation inaccordance with the component type of the corresponding data (S109050).

In case the component type corresponds to IP service information, i.e.,when the component type corresponds to common PLP data, the inputpre-processor (100000) may determine whether or not the IP serviceinformation requires modification (S109060). Thereafter, whenmodification is required, the corresponding IP service information (ESGinformation, bootstrap information, provider information, and so on) maybe generated or modified (S109070). Then, by using the IP stream merger(106050), IP service information that are to be included in the data,which are transmitted to the common PLP, are merged (S109090).

In case the component type does not correspond to IP serviceinformation, i.e., in case the component type corresponds to componentPLP data, the input pre-processor (100000) sets up a physical parameterbased upon the component type, thereby enabling the physical parameterto be signaled to the L1 signaling information (S109080). In otherwords, the input pre-processor (100000) may signal information on acomponent PLP structure to the L1 signaling information, so that thereceiver can process the component PLP corresponding to the service inaccordance with the component structure of the present invention.

In case the output data format corresponds to a GSE stream, the inputpre-processor (100000) performs GSE encapsulation on the processed PLPdata in accordance with the component type (S109100). In case the outputdata format corresponds to an IP GSE stream, this step may also beomitted. Each set of the component PLP data may be outputted to adifferent PLP path (S109110).

The output of the input pre-processor (100000) is outputted to the inputprocessor (100100).

In the description of the present invention, TS or IP or GSE streams maybe converted to n+1 number of streams that can be independentlyprocessed through the input pre-processor (100000) or the inputprocessor (100100). At this point, the stream that is to beindependently processed may correspond to a complete (or whole) TSstream including a plurality of service components, and may alsocorrespond to a TS stream of a minimum unit including only one servicecomponent (e.g., video or audio, and so on). Similarly, the stream thatis to be independently processed may correspond to a complete (or whole)GSE stream including a plurality of service components or a GSE streamincluding only one service component. Furthermore, the stream that is tobe independently processed may also correspond to a complete (or whole)IP stream including a plurality of service components or an IP streamincluding only one service component.

FIG. 14 illustrates a block diagram showing an exemplary structure of aninput processor (100100) according to an embodiment of the presentinvention.

Herein, FIG. 14 shows an exemplary embodiment of an input processor(100100), wherein the number of input streams is equal to 1. When thenumber of input streams is equal to 1, the input processor (100100) mayinclude an input interface module (110100), a CRC-8 encoder (110200), aBB header inserter (110400), a padding inserter (110400), and a BBscrambler (110500). In the description of FIG. 14, the input interfacemodule (110100), the CRC-8 encoder (110200), and the BB header inserter(110400) will be collectively referred to as a mode adaptation module,and the padding inserter (110400) and the BB scrambler (110500) will becollectively referred to as a stream adaptation module.

The input interface module (110100) maps an input stream in internallogical-bit format for performing FEC (BCH/LDPC) encoding in a BICMmodule (100200). More specifically, the interface module (110100) slicesthe input stream to bit units corresponding to a number of bits requiredfor generating a BB (Base Band) frame, so as to map into a BB framepayload. The CRC-8 encoder (110200) performs CRC encoding on the BBframe payload outputted from the interface module (110100), and the BBheader inserter (110300) inserts a header having a fixed size to afore-end portion of the BB frame payload, which is processed with CRCencoding, to generate a BB frame.

In case a data size of the inputted bit stream is smaller than a BBframe designated to FEC, the padding inserter (110400) may insert apadding bit to the BB frame, in order to configure the BB frame. The BBscrambler (110500) may perform a bitwise XOR (Exclusive OR) operation ona bit stream of the BB frame by using a PRBS (Pseudo Random BinarySequence), so as to perform randomization. The operations of the BBscrambler (110500) may reduce PAPR (Peak-to-Average Power Ratio) of anOFDM modulation signal transmitted finally.

FIG. 15 illustrates a block diagram showing an exemplary structure of amode adaptation module of an input processor (100100) respective to amulti PLP input according to another embodiment of the presentinvention. More specifically, FIG. 15 shows an embodiment of a modeadaptation module of the input processor (100100) processing a pluralityof PLPs when a type of input stream is a TS format.

The mode adaptation module may include n+1 number of input interfacemodules (111200-0˜n), n+1 number of input stream sync modules(111210-0˜n), n+1 number of delay compensators (111220-0˜n), n+1 numberof null packet deleters (111230-0-n), n+1 number of CRC (CyclicRedundancy Check) encoders (111240-0˜n), and n+1 number of BB headerinserters (111250-0˜n) operating in parallel to perform mode adaptationon each PLP of the plurality of PLPs.

According to the broadcast signal transmitting apparatus of the presentinvention, by including signaling information that can be commonlyapplied to multiple PLPs, such as a transport layer signal of anMPEG-TS, in a single PLP, and by transmitting the processed PLP, thetransmission efficiency may be increased. As shown in FIG. 15, the PLPs,performs such function, and, in the description of the presentinvention, such PLP is referred to as a common PLP. The remaining Pnumber of PLPs excluding the PLP-0, shown in FIG. 15, may be used forperforming data transmission. And, in the description of the presentinvention, such PLP is referred to as a data PLP. Herein, the examplegiven in FIG. 15 is merely exemplary, and, therefore, a plurality ofcommon PLPs, such as PLP0 of FIG. 15, may be used in the presentinvention.

The input interface modules (111200-0˜n) may slice the input stream ofthe corresponding PLP to a number of bits required for generating the BBframe (Base Band frame), so as to map into a BB frame payload.

The input stream sync modules (111210-0˜n) generate sync timinginformation required to recovery TS or GS streams in a receiver andinsert the sync timing information into a BB frame payload. Furthermore,when the receiver performs service recovery, the input stream syncmodules (11210-0˜n) may generate sync timing information based upon alldelays that may occur in the respective channels and transmissionprocessed, so that the corresponding service can be recovered to theinitial timing. Herein, the sync timing information may correspond to anISCR (Input Stream Clock Reference) information. Moreover, the inputstream sync modules (111210-0˜n) synchronize in the receiver by adding async byte.

When multiple PLPs exist, the delay compensators (111220-0˜n) maycompensate the delay difference between each PLP, so that the frame canbe efficiently configured. More specifically, based upon the sync timinginformation inserted by the input stream sync modules (111210-0˜n), thedelay compensators (111220-0˜n) may delay data on PLPs of group units soas to synchronize the PLPs.

In case of a VBR (variable bit rate) service, the null packet deleters(111230-0˜n) may delete the inserted null packets, so as to increase thetransmission efficiency. At this point, a number of deleted null packets(DNPs) may be inserted in the deleted positions, so as to betransmitted.

The CRC encoders (111240-0˜n) performs CRC encoding on the correspondingframe, in order to enhance the transmission reliability of the BB framepayload, thereby adding CRC data.

The BB header inserters (111250-0˜n) inserts a header having a fixedsize on a fore-end portion of the corresponding BB frame payload, sothat the format of the data field can be identified. Herein, the headermay include diverse information, such as Mode Adaptation Typeinformation indicating whether the stream type the of correspondingstream corresponds to a TS, an IP, or a GS, User Packet Lengthinformation, Data Field Length information, User Packet Sync Byteinformation, start address information of a User Packet Sync Byteincluded in the data field, a high efficiency mode indicator, an inputstream sync field, and so on.

FIG. 15 shows an exemplary case when the input stream type correspondsto a TS, and if the input stream type corresponds to an IP stream or aGSE stream, the delay compensators (111220-0˜n) and the null packetremovers (111230-0˜n) may be omitted. For example, since the IP packetis buffered and reproduced in the receiver in accordance with a timestamp, the data are not required to be delayed, and the null packet isnot required to be added/deleted. Additionally, since the IP packetitself has a CRC, the CRC byte is not required to be added. Accordingly,in the operations of the input processor of FIG. 15, the delaycompensators (111220-0˜n) and the null packet removers (111230-0˜n) maybe omitted, or, in case of the IP stream or GSE stream, the blocks maybe bypassed.

FIG. 16 illustrates an exemplary structure of a stream adaptation moduleof an input processor (100100) respective to a multi PLP input accordingto another embodiment of the present invention.

The stream adaptation module may include a scheduler (120300), n+1number of frame delayers (130100-0˜n), n+1 number of in-bandsignaling/padding inserters (130200-0˜n), and n+1 number of BBscramblers (130300-0˜n).

The scheduler (120300) may perform scheduling in order to allocatemultiple PLPs to each slot of a transmission frame. In case the systemuses a MIMO method, the scheduler (120300) may include a scheduler fordual polarity MIMO. More specifically, the scheduler (120300) maygenerate parameters that can be used by a DEMUX, a cell interleaver, atime interleaver of the BICM module (100200). Herein, examples of suchparameters may include parameters related to a polarity path, such as anH-path and a V-path. Furthermore, the scheduler (120300) enables a cellmapper to map input cells according to scheduling by outputtingL1-dynamic signaling information on a current frame, apart from in-bandsignaling.

The frame delayers (130100-0˜n) may delay input data by one transmissionframe, so that scheduling information respective to a next frame can betransmitted through a current frame, in order to perform in-bandsignaling.

The in-band signaling/padding inserters (130200-0˜n) insert thenon-delayed L1-dynamic signaling information to the data being delayedby one transmission frame. In this case, if surplus space exists withinthe input data, a padding bit may be inserted in the surplus space, orin-band signaling information may be inserted in the surplus space.

In order to minimize the correlation between transmission bit sequences,the BB scramblers (130300-0˜n) perform XOR operation on the input bitstream and PRBS, which are outputted from the in-band signaling/paddinginserters (130200-0˜n), so as to randomize the input bit stream. Afterperforming the scrambling procedure, the PAPR of the OFDM modulationsignal, which is finally transmitted, may be reduced.

Additionally, in addition to in-band signaling, the scheduler (120300)may transmit L1-dynamic signaling information of the current frame tothe cell mapper of the frame builder. The cell mapper uses the inputtedinformation, so as to map the input cells to the transmission frame.

The difference between a stream adaptation module respective to a multiPLP input of FIG. 16 and a stream adaptation respective to a single PLPinput of FIG. 14 is that a scheduler (120300), n+1 number of framedelayers (130100-0˜n), n+1 number of in-band signaling/padding inserters(130200-0˜n), and so on, are added in the stream adaptation module.

Meanwhile, the stream adaptation module of FIG. 16 may further includean L1 signaling generator. In addition to the in-band signalinginformation, the L1 signaling generator generate L1 signalinginformation, which is transmitted through a preamble symbol of thetransmission frame or a data symbol, which is being spread. Such L1signaling information includes L1-pre-signaling information andL1-post-signaling information. The L1 signaling generator outputs eachof the L1-pre-signaling information and the L1-post-signalinginformation.

Additionally, the present invention may further include a first BBscrambler scrambling the L1-pre-signaling information and a second BBscrambler scrambling the L1-post-signaling information at the outputtingend of the L1 signaling generator. In this case, the L1-pre-signalinginformation may be scrambled by the first BB scrambler, and theL1-post-signaling information may be scrambled by the second BBscrambler, both by performing XOR operation with the PRBS. According toanother embodiment of the present invention, the L1 signaling generatormay output the L1 signaling information, which includes theL1-pre-signaling information and the L1-post-signaling information, andone BB scrambler may also scramble the outputted L1 signalinginformation.

Meanwhile, in the present invention, the MISO method may beindependently applied for each set of PLP data, and the MIMO method mayalso be applied.

According to an embodiment of the present invention, the BICM module mayperform MIMO encoding on the MIMO PLP data that are to be transmitted byusing the MIMO method, and the OFDM generator may perform MISO encodingon the MISO PLP data that are to be transmitted by using the MISOmethod.

According to another embodiment of the present invention, the BICMmodule may perform MIMO encoding on the MIMO PLP data that are to betransmitted by using the MIMO method, and the BICM module may alsoperform MISO encoding on the MISO PLP data that are to be transmitted byusing the MISO method. In this case, the MISO encoding process may beomitted in the OFDM generator.

FIG. 17 illustrates a block diagram showing the structure of a BICMmodule (100200) according to an embodiment of the present invention.Herein, the BICM module performs bit interleaving on the multiple setsinput-processed PLP data, the L1-pre-signaling information, and theL1-post-signaling information and performs encoding for errorcorrection.

For this, according to the embodiment of the present invention, the BICMmodule of FIG. 17 includes a first BICM encoding block (130600)processing MISO PLP data, a second BICM encoding block (130700)processing MIMO PLP data, and a third BICM encoding block (130800)processing signaling information. The third BICM encoding block (130800)then includes a first encoding block for processing L1-pre-signalinginformation and a second encoding block for processing L1-post-signalinginformation.

The signaling information may be processed with MISO or MIMO processingby the OFDM generator. However, since the signaling information includesinformation that are required by the receiver in order to recover thePLP data included in the transmission frame, a greater robustnessbetween the transmission and the reception as compared to that of thePLP data is required. Therefore, according to the embodiment of thepresent invention, the OFDM generator may process the signalinginformation by using the MISO method.

Hereinafter, the data processing method of each block will be described.

The first BICM encoding block (130600) includes an FEC (Forward ErrorCorrection) encoder (131100-0), a bit interleaver (131200-0), a demux(131300-0), a constellation mapper (131400-0), a cell interleaver(131600-0), and a time interleaver (131700-0).

The FEC encoder (131100-0) adds a redundancy to an input bit stream, sothat the receiver can perform correction on an error occurring on thetransmission channel with respect to input processed PLP data and may,then, perform bit stream encoding at a coding rate, such as 1/4, 1/3,2/5. For example, the FEC encoder (131100-0) may use a BCH(Bose-Chaudhuri-Hocquengham)/LDPC (Low Density Parity Check) code, so asto add redundancy for error correction and to perform encoding.

The bit interleaver (131200-0) may perform bit interleaving in a singleFEC block unit on the PLP data, which are processed with FEC encoding,so that the error can have robustness against a burst error, which mayoccur during transmission. In this case, the bit interleaver (131200-0)may perform bit interleaving by using two FEC block units. And, asdescribed above, when bit interleaving is performed by using two FECblock units, cells forming a pair in the frame builder, which will bedescribed later on, may each be generated from a different FEC block.Therefore, the broadcasting signal receiver may ensure diversity so asto enhance the receiving performance.

The demux (131300-0) performs demultiplexing in a single FEC block unit.According to an embodiment of the present invention, the demux(131300-0) may adjust the order of the bits configuring a cell, so as tocontrol the robustness of the bit, thereby outputting the cell includingthe bits. More specifically, the demux (131300-0) adjusts the bit outputorder in order to perform dispersed positioning on the distribution ofthe data reliability, which is generated during the LDPC encodingprocess, when the constellation mapper (131400-0) performs symbolmapping in a later process. The demux (131300-0) may performdemultiplexing by using two FEC blocks. As described above, whendemultiplexing is performed by using two FEC blocks, the cellsconfiguring a pair in the frame builder, which will be described indetail later on, may each be generated from a different FEC block.Therefore, the receiver may ensure diversity, so as to gain a moreenhanced receiving performance.

The constellation mapper (131400-0) maps the demultiplexed bit unit PLPdata to the constellation. In this case, the constellation mapper(131400-0) may rotate the constellation by a predetermined angle inaccordance with the modulation type. The rotated constellations may beexpressed as an I-phase (In-phase) element and a Q-phase(Quadrature-phase) element, and the constellation mapper (131400-0) maydelay only the Q-phase element by an arbitrary value. Thereafter, theconstellation mapper (131400-0) may use the In-phase element and thedelayed Q-phase element, so as to remap the demultiplexed PLP data to anew constellation.

The cell interleaver (131600-0) may perform interleaving in cell unitson the PLP data mapped or remapped to the constellation, and the timeinterleaver (131700-0) may perform interleaving on the cell-interleavedPLP data in time units, so as to output the time-interleaved PLP data tothe frame builder. In this case, the time interleaver (131700-0) mayperform interleaving by using 2 FEC blocks. By performing thisprocedure, since the cells configuring a pair in the frame builder,which will be described later on, may each be generated from a differentFEC block, the receiver may ensure diversity so as to enhance thereceiving performance.

The second BICM encoding block (130700) includes an FEC encoder(131100-1), a bit interleaver (131200-1), a demux (131300-1), a firstconstellation mapper (131400-1) and a second constellation mapper(131400-2), an MIMO encoder (131500-1), a first cell interleaver(131600-1), a second cell interleaver (131600-2), a first timeinterleaver (131700-1) and a second time interleaver (131700-2). The FECencoder (131100-1) and the bit interleaver (132100-1) perform the samefunctions as the FEC encoder (131100-0) and the bit interleaver(131200-0) of the first BICM encoding block (130600).

The demux (131300-1) may perform the same functions as the demux(131300-0) of the first BICM encoding block (130600) and mayadditionally perform demultiplexing on the PLP data, so as to output thedemultiplexed PLP data through 2 input paths, which are required for theMIMO transmission. In this case, the transmission characteristics of thedata being transmitted through each input path may be identical to oneanother or may be different from one another.

For example, in case the transmission characteristics of the data beingtransmitted through each of the 2 input paths are different from oneanother, the demux (131300-1) may randomly allocate (or assign) bitwords of the PLP data corresponding to the cell, which is included inone FEC block, to each input path.

In another example, in case the transmission characteristics of the databeing transmitted through each of the 2 input paths are identical to oneanother, the second constellation mapper (131400-2), the second cellinterleaver (131600-2), and the second time interleaver (131700-2),which are marked in dotted lines may not be used.

The first constellation mapper (131400-1) and the second constellationmapper (131400-2) perform the same functions as the constellation mapper(131400-0) of the first BICM encoding block (130600).

The MIMO encoder (131500-1) may apply a MIMO encoding matrix on the PLPdata, which are mapped to the first constellation mapper (131400-1) andthe second constellation mapper (131400-2), so as to perform MIMOencoding on the processed data, thereby outputting the MIMO encoded datato 2 paths. The MIMO encoding method will be described in more detaillater on.

According to an embodiment of the present invention, the first cellinterleaver (131400-1) and the second cell interleaver (131400-2) mayperform cell interleaving only on the PLP data corresponding to half thesize of an FEC block, among the PLP data being MIMO encoded and inputtedthrough each path. Accordingly, the cell interleaving process performedby the first cell interleaver (131400-1) and the second cell interleaver(131400-2) may have the same effect as the interleaving procedureperformed by the cell interleaver (131400-0) of the MISO method includedin the first BICM encoding block (130600). Additionally, the first cellinterleaver (131400-1) and the second cell interleaver (131400-2) areadvantageous in that additional memory are not assigned (or allocated)to the first cell interleaver (131400-1) and the second cell interleaver(131400-2), in order to process the data of multiple paths, and thatcell interleaving may be performed by using the memory settings of thecell interleaver (131400-0).

The first time interleaver (131700-1) and the second time interleaver(131700-1) perform the same functions as the time interleaver (131700-0)of the first BICM encoding block (130600). Also, the first timeinterleaver (131700-1) and the second time interleaver (131700-2) mayperform time interleaving on the PLP data being inputted through eachpath by using the same method, or may perform time interleaving by usingdifferent methods.

The third BICM encoding block (130800) includes a first encoding blockprocessing L1-pre-signaling information and a second encoding blockprocessing L1-post-signaling information.

The first encoding block may include an FEC encoder (132100-0), aconstellation mapper (132400-0), a cell interleaver (132500-0), and atime interleaver (132600-0). The second encoding block may include anFEC encoder (132100-1), a bit interleaver (132200), a demux (132300), aconstellation mapper (132400-1), a cell interleaver (132500-1), and atime interleaver (132600-1).

In order to decode the L1 signaling information and data, the receiveris required to accurately and swiftly decode the L1-pre-signalinginformation. Therefore, according to an embodiment of the presentinvention, in order to allow the receiver to accurately and swiftlydecode the L1-pre-signaling information, the present invention will notperform bit interleaving and demultiplexing on the L1-pre-signalinginformation.

For the description on the operations of each block included in thefirst encoding block and the second encoding block, reference may bemade to the description on the operations of the same blocks included inthe first BICM encoding block (130600). And, therefore, detaileddescription of the same will be omitted. However, 2 FEC encoders(132100-0˜1) perform FEC encoding including shortening and puncturing oneach of the inputted L1-pre-signaling information and L1-post-signalinginformation. The FEC encoding process may include BCH encoding and LDPCencoding.

Meanwhile, in the present invention, instead of the input processor, anL1 signaling generator may be located in front of the 2 FEC encoders(132100-0˜1) of the first BICM encoding module. Moreover, a first BBscrambler and a second BB scrambler may be further included at theoutputting end of the L1 signaling generator. The description on theoperations of the L1 signaling generator and the first and second BBscramblers is identical to the description on the operations of thecorresponding blocks within the input processor. According to anotherembodiment of the present invention, the L1 signaling informationincluding the L1-pre-signaling information and the L1-post-signaling maybe scrambled by using one BB scrambler.

The demuxes (131300-0, 131300-1, 132300) within the first to third BICMencoding blocks of FIG. 17 may also be referred to as bit-cell demuxes.

At this point, the first BICM encoding block (130600) outputs PLP data,which are to be outputted by using the MISO method, through 1 path(STX_k), and the second BICM encoding block (130700) outputs PLP data,which are to be outputted by using the MIMO method, through 2 paths(STX_m, STX_m+1). Additionally, the third BICM encoding block (130800)outputs each of the L1-pre-signaling information and theL2-post-signaling information through one path (STX_pre, STX_post). Forsimplicity of the description of the present invention the pathcorresponding to the STX_k, STX_m, STX_pre, STX_post will be referred toas a first path, and the path corresponding to the STX_m+1 will bereferred to as a second path.

In the structure shown in FIG. 17, the PLP data or signaling data areprocessed in symbol units after being mapped to the constellation.Accordingly, the second BICM encoding block (130700) performs MIMOencoding, cell interleaving, time interleaving on the MIMO PLP data inOFDM units. In this case, the time deinterleaver, the celldeinterleaver, and the MIMO decoder of the broadcasting signal receiverprocess the reception data in symbol units.

According to another embodiment of the BICM module shown in FIG. 17, theMIMO encoder may be provided at the outputting ends of the first timeinterleaver and the second time interleaver.

In this case, the BICM decoder of the broadcast signaling receivershould first perform MIMO decoding on the MIMO PLP data beforeperforming any other operations. And, the MIMO decoded data areoutputted in bit units. Thereafter, the BICM decoder of the broadcastingsignal receiver may perform time deinterleaving and cell deinterleavingon the MIMO decoded data. However, since the data outputted in bit unitsare being inputted, information on the symbol units of the inputted datais required. More specifically, since the broadcasting signal receivershould to store information on symbol mapping of the input bits, whichare required in the deinterleaving process, the complexity in the memoryof the receiver may be increased.

Conversely, if the MIMO encoder is located between the constellationmapper and the cell interleaver, as shown in FIG. 17, the respectiveBICM decoder of the broadcasting signal receiver may perform MIMOdecoding on the symbol unit data, after performing both timedeinterleaving and cell deinterleaving in symbol units. In this case,since the bit unit data being processed with MIM decoding are processedwith the constellation demapping procedure, additional (or separate)information on symbol mapping is not required. Accordingly, if the MIMOencoder is located after the constellation mapper, the complexity in thememory of the receiver may be reduced, as compared to when the MIMOencoder is located after the time interleaver.

FIG. 18 illustrates a block diagram showing the structure of a framebuilder according to an embodiment of the present invention. Herein, theframe builder is adequate for processing the output of the BICM moduleshown in FIG. 17. In the present invention, the frame builder will alsobe referred to as a frame mapper.

The frame builder of FIG. 18 includes a first frame building block(133100) receiving MISO PLP data, MIMO PLP data, L1-pre-signaling data,and L1-post-signaling data of the first path, and a second framebuilding block (133500) receiving MIMO PLP data of the second path. Thedata of the first path are processed with a modulation procedure in theOFDM generator, so as to be transmitted through the first antenna(Tx_1), and after being processed with the modulation procedure in theOFDM generator, the data of the second path are transmitted through thesecond antenna (Tx_2).

According to an embodiment of the present invention, the first framebuilding block (133100) includes a delay compensator (133200), a firstcell mapper (133200), and a first frequency interleaver (133400), andthe second frame building block (133500) includes a second cell mapper(133600) for processing data being inputted through the second path anda second frequency interleaver (133700).

The first cell mapper (133300) and the first frequency interleaver(133400) and the second cell mapper (133600) and the second frequencyinterleaver (133700) may operate identically with respect to the firstpath and the second path or may operate independently from one anotherwith respect to the first path and the second path.

Hereinafter, the data processing method of the blocks included in thefirst frame building block (133100) and the second frame building block(133500) will be described.

In order to perform cell mapping, the delay compensator (133200)compensates for the delay generated in the signaling information andmatches the time synchronization with the inputted PLPs. Morespecifically, a delay corresponding to one transmission frame in theL1-pre-signaling data or the L1-post-signaling data and a delayoccurring due to the encoding process of the third BICM encoding block(130800) are both compensated. Since the L1 signaling information mayinclude not only the information on the current information frame butalso the information on the next transmission frame, during the inputprocessing procedure, the L1 signaling information is delayed by oneframe than the PLP data that are currently being inputted. By performingsuch procedure, one transmission frame may transmit L1 signalinginformation including both information on the current transmission frameand information on the next transmission frame.

The first cell mapper (133300) and the second cell mapper (133600) mapthe symbol unit PLP data and the L1 signaling data being inputtedthrough each path to subcarriers of the OFDM symbol, which is includedin the transmission frame, in cell units in accordance with thescheduling information included in the signaling information.

Additionally, the first cell mapper (133300) and the second cell mapper(133600) respectively map the MISO PLP data and the MIMO PLP data tosubcarriers of one OFDM symbol in cell units.

The PLP data, which are being inputted to the first cell mapper (133300)and the second cell mapper (133600) through the first path and thesecond path may include common PLP data, MISO, MIMO PLP data, and eachsub-slice processor may perform sub-slicing on the PLP data cells, inorder to gain a diversity effect, so as to map the processed PLP datacell within the transmission frame.

Additionally, although the MISO PLP data and the L1-pre-signaling andpost-signaling data are inputted only through the first path, since theMIMO PLP data are inputted through both the first path and the secondpath, the operation of the cell mapper may vary depending upon whichdata are being inputted.

Hereinafter, the detailed operations will be described.

First of all, the first cell mapper (133300) and the second cell mapper(133600) may each receive the same MISO PLP data that are inputtedthrough the first path, and the first cell mapper (133300) and thesecond cell mapper (133600) may also receive the same L1-pre and postsignaling information, which are outputted from the delay compensator(133200). In this case, the first cell mapper (133300) and the secondcell mapper (133600) may map each set of input data, so that thecorresponding data can be allocated to the subcarrier of the OFDM symbolwith the transmission frame.

Secondly, among the first cell mapper (133300) and the second cellmapper (133600), only the first cell mapper (133300) may receive theMISO PLP data and the delay-compensated L1-pre and post signaling data.In this case, the second cell mapper (133600) may perform mapping onlyon the MIMO PLP.

The first frequency interleaver (133400) and the second frequencyinterleaver (133700) may perform frequency interleaving on the databeing inputted through each path in cell units, and may output thefrequency interleaved data to the OFDM generator through each path.

In this case, the first frequency interleaver (133400) and the secondfrequency interleaver (133700) perform interleaving on the cellspositioned in the transmission frame within the frequency domain basedupon the OFDM symbol. Additionally, when the second cell mapper (133600)receives only the MIMO PLP data, the second frequency interleaver(133700) may also perform interleaving only on the MIMO PLP data.

FIG. 19 illustrates a block diagram showing the structure of an OFDMgenerator according to an embodiment of the present invention, which isadequate for processing the output of the frame builder shown in FIG.18. Most particularly, FIG. 19 shows an example of transmitting abroadcasting signal through 2 transmission antennae by using the MISO orMIMO method. According to the embodiment of the present invention, apolarity multiplexing MIMO method is used in the present invention.

The OFDM generator of FIG. 19 is configured of an MISO encoder (134100),2 pilot inserters (134100-0, 134100-1), 2 IFFT modules (134200-0,134200-1), 2 PAPR reduction modules (134300-0, 134300-1), 2

GI inserting modules (134400-0, 134400-1), 2 P1 symbol inserting modules(134500-0, 134500-1), 2 AP1 symbol inserting modules (134600-0,134600-1), and 2 DACs (134700-0, 134700-1). In the present invention, ablock modulating a broadcasting signal that is to be transmitted througha first transmission antenna (Tx1) will be referred to as a firsttransmitting unit, and a block modulating a broadcasting signal that isto be transmitted through a second transmission antenna (Tx2) will bereferred to as a second transmitting unit. The first transmitting unitincludes a pilot inserter (134100-0), an IFFT module (134200-0), a PAPRreduction module (134300-0), a GI inserting module (134400-0), a P1symbol inserting module (134500-0), an AP1 symbol inserting module(134600-0), and a DAC (134700-0). The second transmitting unit includesa pilot inserter (134100-1), an IFFT module (134200-1), a PAPR reductionmodule (134300-1), a GI inserting module (134400-1), a P1 symbolinserting module (134500-1), an AP1 symbol inserting module (134600-1),and a DAC (134700-1).

In order to perform transmission through 2 transmission antennae, theMISO encoder (134100) performs MISO encoding, so that transmissiondiversity can be gained for signals being inputted through the first andsecond paths. Then, the MISO encoder may output the processed signals toeach pilot inserter (134100-0, 134100-1). If data MIMO-encoded by theBICM module are inputted, the MISO encoder (134100) may bypass the inputdata to the pilot inserters (134100-0, 134100-1).

More specifically, if the data being inputted through the first path andthe second path correspond to MISO PLP data or L1-pre and post signalingdata, the MISO encoder (134100) may use an MISO encoding matrix so as toperform MISO encoding in OFDM symbol units, thereby outputting theprocessed data to the pilot inserters (134100-0, 134100-1). In thiscase, the data may also be inputted to the MISO encoder (134100) onlythrough any one of the first path and the second path. According to theembodiment of the present invention, examples of the MISO encodingmatrix may include OSTBC (Orthogonal Space-Time Block Code)/OSFBC(Orthogonal Space Frequency Block Code or Alamouti code).

The pilot inserters (134100-0, 134100-1) may insert a pilot signalhaving a specific pilot pattern in a respective position within thesignal frame, so that the receiver can perform transmission channelestimation and time/frequency synchronization, thereby outputting theprocessed data to the IFFT modules (134200-0, 134200-1). At this point,the pilot pattern information may be signaled to the AP1 signalinginformation and may also be signaled to the L1 signaling information.Alternatively, the pilot pattern information may be signaled to both theAP1 signaling information and the L1 signaling information.

By performing inverse fast fourier transform, the IFFT modules(134200-0, 134200-1) convert each signal having a pilot inserted thereinto time domain signals, thereby outputting the processed signals to thePAPR reduction modules (134300-0, 134300-1).

The PAPR reduction module (134300-0, 134300-1) may reduce the PAPR ofthe time domain signals, thereby outputting the processed signals to theGI inserting modules (134400-0, 134400-1). The PAPR reduction modules(134300-0, 134300-1) may use at least one of an ACE (ActiveConstellation Extension) method or a Tone Reservation method, so as toreduce the PAPR from the modulated OFDM symbol. Additionally, necessary(or required) information may be fed-back to the pilot inserters(134100-0, 134100-1) in accordance with a PAPR reduction algorithm.

By copying the last portion of an effective OFDM symbol to a frontportion of the corresponding OFDM symbol, the GI inserting modules(134400-0, 134400-1) may insert a guard interval in a cyclic prefixformat, thereby outputting the processed symbol (or data) to the P1symbol inserting modules (134500-0, 134500-1). The GI information issignaled to the L1 pre signaling information. And, a portion of the GIinformation is signaled to the P1 signaling information.

The P1 symbol inserting modules (134500-0, 134500-1) may insert a P1symbol in a starting portion of each signal frame, thereby outputtingthe processed data (or signal) to the AP1 symbol inserting modules(134600-0, 134600-1).

The AP1 symbol inserting modules (134600-0, 134600-1) insert an AP1symbol after each P1 symbol, thereby outputting the processed data tothe DACs (134700-0, 134700-1). Herein, the insertion of the P1 symbolsand the AP1 symbols may be performed by the P1 symbol inserting modules(134500-0, 134500-1), and, in this case, the AP1 symbol insertingmodules (134600-0, 134600-1) may be omitted.

The DACs (134700-0, 134700-1) may first convert the each signal framehaving the AP1 symbol inserted therein to analog signals, therebytransmitting the converted signal through the corresponding transmissionantenna (Tx1, Tx2).

Meanwhile, according to the embodiment of the present invention, theMIMO encoder (131500-1) within the BICM module of FIG. 17 may performMIMO encoding by using an MIMO encoding matrix. Hereinafter, the MIMOencoder indicates the MIMO encoder (131500-1) within the BICM module ofFIG. 17. The MIMO encoding matrix according to the present invention mayinclude spatial multiplexing, a GC (Golden code), a Full-rate fulldiversity code, a Linear dispersion code, and so on. Alternatively, thepresent invention may use encoding matrices according to a firstembodiment to a third embodiment of the present invention, which aredescribed below, so as to perform MIMO encoding.

More specifically, in order to ensure low system complexity, high datatransmission efficiency, and high signal recovery performance in variouschannel environments, multiple input signals may be processed with MIMOprocessing, in accordance with a MIMO matrix and a parameter value ofthe MIMO matrix, thereby being capable of outputting multipletransmission signals. According to the embodiment of the presentinvention, the broadcasting signal transmitting device may use the MIMOencoder, so as to perform MIMO encoding on a broadcasting signal and totransmit the processed signal through a plurality of transmissionantennae, and the broadcasting signal receiving device may use the MIMOdecoder, so as to perform MIMO decoding on the broadcasting signal,which is received through a plurality of reception antennae. In thepresent invention, the MIMO encoder may also be referred to as an MIMOprocessor, and the MIMO decoder may also be referred to as an ML(Maximum Likelihood) detector (or ML decoder).

At this point, the modulation method may be expressed as M-QAM(Quadrature Amplitude Modulation) or N-QAM. More specifically, when M(or N) is equal to 2, the modulation method may be expressed as 2-QAM,which indicates a BPSK (Binary Phase Shift Keying) method, and when M(or N) is equal to 4, the modulation method may be expressed as 4-QAM,which indicates QPSK (Quadrature Phase Shift Keying). Moreover, when M(or N) is equal to 16, the modulation method may be expressed as 16-QAM,when M (or N) is equal to 64, the modulation method may be expressed as64-QAM, and when M (or N) is equal to 256, the modulation method may beexpressed as 256-QAM. Herein, M, N each indicates a number of symbolsbeing used for modulation.

For example, M+M QAM MIMO indicates that QAM symbols, which are used forMIMO encoding and MIMO decoding, use the same M-QAM. In another example,M+N QAM MIMO indicates that QAM symbols, which are used for MIMOencoding and MIMO decoding, use different M-QAM and N-QAM.

In the present invention, a channel environment havingtransmission/reception paths that are independent from one another maybe referred to as un-correlated channels, and a channel environment,such as an LOS (Line Of Sight) environment, having high correlationbetween the channels of the transmission/reception paths may be referredto as fully correlated channels.

In the present invention, in order to overcome the case when thecorrelation between the MIMO channels is equal to 1, i.e., when the MIMOchannel corresponds to a fully correlated channel, the MIMO systemaccording to the present invention may be designed so that a signal,which is received after passing through a channel, can satisfy thefollowing conditions (or requirements).

1) A received signal should be capable of expressing both originalsignals.

2) A minimum Euclidean distance of the received signal should beincreased, so that a symbol error rate can be reduced. Herein, aEuclidean distance refers to a distance between coordinates over aconstellation.

3) A hamming distance characteristic of the received signal should beadvantageous, so that the bit error rate can be reduced. Herein, when abit value corresponding to binary codes each having the same number ofbits do not match, the Hamming distance indicates a number of binarycodes having non-matching bit values.

In order to meet with the above-described requirements, the presentinvention proposes a MIMO encoding method using an MIMO encoding matrix,which includes an encoding parameter (also referred to as an encodingcoefficient) a, as shown below in Equation 2.

$\begin{matrix}\begin{bmatrix}1 & a \\a & {- 1}\end{bmatrix} & {{Equation}\mspace{14mu} 2}\end{matrix}$

When an MIMO encoder performs encoding on input signals S1 and S2 byusing an MIMO encoding matrix, as shown in Equation 2, the receptionsignal 1 (Rx1) and the reception signal 2 (Rx2), which are received byreception antenna 1 and reception antenna 2, may be calculated by usingEquation 3 shown below. And, most particularly, in case the MIMO channelcorresponds to a fully correlated channel, the signals are calculated byusing the last line shown in Equation 3.Rx ₁ =h ₁₁(S1+aS2)+h ₂₁(aS1−S2)Rx ₂ =h ₁₂(S1+aS2)+h ₂₂(aS1−S2)R=Rx ₁ =Rx ₂ =h{(a−1)S2}  Equation 3

First of all, in case the MIMO channel corresponds to an un-correlatedchannel, the reception signal 1 (Rx1) may be calculated asRx1=h₁₁(S1+a*S2)+h₂₁(a*S1−S2), and the reception signal 2 (Rx2) may becalculated as Rx2=h₁₂(S1+a*S2)+h₂₂(a*S1−S2), so that S1 and S2 can havethe same power. Accordingly, all of the gain of the MIMO system may beused as in the SM method.

Meanwhile, when the MIMO channel corresponds to a fully correlatedchannel, the reception signals (R=Rx1=Rx2) may be acquired asR=h{(a+1)S1+(a−1)S2}. Thus, S1 and S2 may be separately acquired.Herein, S1 and S2 may also be designed to have different power levels,and by using such different power levels robustness may be ensured.

In other words, the MIMO encoder may encoder input signals, so thatinput signals S1 and S2 can have different power levels, in accordancewith an encoding parameter (also referred to as an encoding coefficient)a, and so that S1 and S2 can also be received in different distributionformats in a fully correlated channel. For example, by performing anencoding process on S1 and S2, so that S1 and S2 can have differentpower levels, and by transmitting the encoded S1 and S2 to aconstellation having different Euclidean distances due to anormalization process, even when signals go through a fully correlatedchannel, the receiver may separate (or divide) the input signals andrecover the separated signals accordingly.

Based upon a normalization factor, the MIMO encoding matrix of Equation3 may be expressed as shown below in Equation 4.

$\begin{matrix}{{\frac{1}{\sqrt{1 + a^{2}}}\begin{bmatrix}1 & a \\a & {- 1}\end{bmatrix}} = {\quad{\begin{bmatrix}\frac{1}{\sqrt{1 + a^{2}}} & \frac{a}{\sqrt{1 + a^{2}}} \\\frac{a}{\sqrt{1 + a^{2}}} & \frac{- 1}{\sqrt{1 + a^{2}}}\end{bmatrix} = \begin{bmatrix}{\cos\;\theta} & {\sin\;\theta} \\{\sin\;\theta} & {{- \cos}\;\theta}\end{bmatrix}}}} & {{Equation}\mspace{14mu} 4}\end{matrix}$

A MIMO encoding method of the MIMO encoder, which uses the MIMO encodingmatrix shown in Equation 4, may be considered as a method of rotatinginput signals by an arbitrary angle (Theta), which can be expresses asan encoding parameter a, so as to divide the signal into a cosineelement of the rotated signal and a sine element (or real number elementand imaginary (or false) number element) and to assign +/− signs to eachof the divided elements, thereby transmitting the processed signal toanother antenna. For example, the MIMO encoder may perform encoding sothat a cosine element of input signal S1 and a sine element of inputsignal S2 can be transmitted to one transmission antenna, and that asine element of input signal S1 and a cosine element, having a − signadded thereto, of input signal S2 can be transmitted to anothertransmission antenna. A rotation angle may vary depending upon a changein an encoding parameter value a, and power distribution between inputsignals S1 and S2 may vary depending upon a value and angle of thecorresponding parameter. Since the varied power distribution may beexpressed as a distance (i.e., Euclidean distance) between symbolcoordinates in a constellation. Even if the input signals pass through afully correlated channel from the receiving end, such encoded inputsignals may be expressed in the form of a different constellation, sothat the input signals can be identified, divided, and recovered.

In other words, since a Euclidean distance between transmission signalsvaries to a level corresponding to the distribution of the varied power,the transmission signals received by the receiving end may be expressedin the form of distinguishable constellations each having a differentEuclidean distance. More specifically, the MIMO encoder may encode inputsignal S1 and input signal S2 as a signal having another Euclideandistance in accordance with the value a. And, such encoded transmissionsignals may be received by the receiving end in distinguishable (oridentifiable) constellations and may be recovered accordingly.

The MIMO encoding of the input signal, which is performed by using theabove-described MIMO encoding matrix, may be expressed as shown below inEquation 5.

$\begin{matrix}{\begin{bmatrix}{X\; 1} \\{X\; 2}\end{bmatrix} = {{\frac{1}{\sqrt{1 + a^{2}}}\begin{bmatrix}1 & a \\a & {- 1}\end{bmatrix}}\begin{bmatrix}{S\; 1} \\{S\; 2}\end{bmatrix}}} & {{Equation}\mspace{14mu} 5}\end{matrix}$

In Equation 5, S1 and S2 represent normalized QAM symbols of aconstellation, to which input signal S1 and input signal S2 are mappedby a constellation mapper of a MIMO path. And, each of X1 and X2respectively represents a MIMO-encoded symbol. In other words, the MIMOencoder may apply the matrix, which is shown in Equation 5, to a 1^(st)input signal including symbols corresponding to S1 and to a 2^(nd) inputsignal including symbols corresponding to S2, so as to transmit a 1^(st)transmission signal including symbols corresponding to X1 and symbols ofa transmission signal X2 including symbols corresponding to X2.

The MIMO encoder may perform MIMO encoding on input signals by suing theabove-described MIMO encoding matrix, and may also perform encoding byadditionally adjusting an encoding parameter value a. More specifically,the consideration and adjustment of an additional data recoveryperformance of the MIMO transmitting and receiving system may beoptimized by adjusting the encoding parameter value a. And, this willhereinafter be described in more detail.

1. First Embodiment MIMO Encoding Method of Optimizing an EncodingParameter Value a Based Upon a Euclidean Distance (Fully Correlated MIMOChannel)

The value a, which corresponds to an encoding parameter, may becalculated by using the above-described MIMO encoding matrix whileconsidering the Euclidean distance. According to the first embodiment ofthe present invention, a signal that is combined in the receiving end,after passing through a fully correlated MIMO channel, may be given aEuclidean distance, such as a QAM signal.

The first embodiment of the present invention proposes a method ofoptimizing the value a, so that each symbol included in a symbolconstellation of reception signals, which have passed through the fullycorrelated channel, can have the same Euclidean distance. Morespecifically, when the MIMO encoder uses the above-described MIMO matrixso as to encode the input signals, the MIMO encoder may calculate ordetermine the value of the encoding parameter a, so that the Euclideandistance between the reception symbols can be consistent (or equal) inthe constellation of the reception signals (i.e., a combined signal ofthe 1^(st) transmission signal St1 and the 2^(nd) transmission signalSt2), which have passed through the fully correlated channel. And,accordingly, the MIMO encoder may perform an encoding process. Suchvalue a may be expressed as Equation 6 shown below, in accordance with acombination of the modulation methods.

$\begin{matrix}{a = \left\{ \begin{matrix}{3,} & {{{for}\mspace{14mu}{QPSK}} + {QPSK}} \\{{\left( {4 + \sqrt{5}} \right)\text{/}\left( {4 - \sqrt{5}} \right)},} & {{{for}\mspace{14mu}{QPSK}} + {16{QAM}}} \\{0.6,} & {{{for}\mspace{14mu} 16{QAM}} + {16{QAM}}}\end{matrix} \right.} & {{Equation}\mspace{14mu} 6}\end{matrix}$

In other words, since the distribution and constellation of atransmission and reception symbol vary depending upon the modulationmethod of reception signals and the combination of the receptionsignals, the value a may also be varied in order to optimize theEuclidean distance.

In other words, in case of the first embodiment of the presentinvention, for example, in a signal wherein a 1^(st) input signal of4-QAM and a 2^(nd) input signal of 4-QAM are MIMO-encoded and combinedwith outputted 1^(st) transmission signal and 2^(nd) transmissionsignals, the value a may be determined so that the constellation of thecombined signal is identical to the constellation of a 16-QAM signal.The MIMO encoding method according to the first embodiment of thepresent invention shows a more excellent SNR performance as compared towhen using the GC method or the SM method in the fully correlated MIMOchannel. Most particularly, the SNR gain according to the firstembodiment of the present invention becomes higher as the coding rate ofthe outer code increases. Conversely, in case of the SM method, in acoding rate of 2/5 or higher, decoding cannot be performed at all in thefully correlated channel, and, regardless of the SNR, even the servicereception cannot be performed. Additionally, the MIMO encoding methodaccording to the first embodiment of the present invention shows thesame performance in an un-correlated channel as the SM method, and theperformance is more excellent as compared to the other methods.Therefore, the MIMO encoding method according to the first embodiment ofthe present invention may provide a better performance by using a systemhaving a lower complexity level as compared to the GC method. And, theMIMO encoding method according to the first embodiment of the presentinvention may provide a more excellent performance in the fullycorrelated channel, as compared to when using the SM method having asimilar complexity level.

According to another embodiment of the present invention, whenperforming MIMO encoding, a GC subset may be used as the MIMO encodingmatrix. And, in this case, the MIMO encoding matrix may be expressed asshown below in Equation 7.

$\begin{matrix}{{\begin{bmatrix}\alpha & {\alpha\;\theta} \\{i\;\overset{\_}{\alpha}} & {i\overset{\_}{\;\alpha}\overset{\_}{\theta}}\end{bmatrix}\begin{bmatrix}{S\; 1} \\{S\; 2}\end{bmatrix}},{\alpha = {1 + {\left( {1 - \theta} \right)i}}},{\overset{\_}{\alpha} = {1 + {\left( {1 - \overset{\_}{\theta}} \right)i}}},{\theta = \frac{1 + \sqrt{5}}{2}},{\overset{\_}{\theta} = \frac{1 - \sqrt{5}}{2}}} & {{Equation}\mspace{14mu} 7}\end{matrix}$

In case of using an encoding matrix of Equation 7, the performance isshown to be better than the first embodiment of the present invention.

When the MIMO encoding process using the GC subset performed in thefully correlated MIMO channel is compared with the MIMO encoding processperformed according to the first embodiment of the present invention (SMOPT1) in the fully correlated MIMO channel, in case of using the firstembodiment of the present invention (SM OPT1), a minimum Euclideandistance within the constellation of the reception signal may be greaterthan the case of using the GC subset. However, the SNR performancerespective to the case of using the GC subset (SM OLDP Golden) is shownto be better than the case of using the first embodiment of the presentinvention.

2. Second Embodiment MIMO Encoding Method Considering Gray Mapping inAddition to a Euclidean Distance

The second embodiment of the present invention proposes a MIMO encodingmethod enabling a reception signal, which has passed through the fullycorrelated channel in a state when the value a is determined to have avalue that can optimize the Euclidean distance, as in the firstembodiment of the present invention, to have gray mapping appliedthereto.

In the MIMO encoding method according to the second embodiment of thepresent invention, among the input signals S1 and S2, signs of the realnumber part and the imaginary number part of input signal S2 may bechanged in accordance with the S1 value, so that gray mapping can beperformed in the receiving end. The change in the data value included inS2 may be performed by using the method shown below in Equation 8.

More specifically, the MIMO encoder may use the MIMO encoding matrixused in the first embodiment of the present invention and may performMIMO encoding by changing the sign of the input signal S2 in accordancewith the value of S1. In other words, as shown in Equation 8, afterdeciding the sign of input signal S2 in accordance with the sign ofinput signal S1, MIMO encoding matrix may be applied to the decidedinput signal S1 and input signal S2, as described above, so that 1^(st)transmission signal St1 and 2^(nd) transmission signal St2 can beoutputted.S1=b ₀ b ₁ . . . b _(N-1) , N=log₂ M, M=QAM size of S1real(S1)=b ₀ b ₂ . . . b _(N-2)imag(S1)=b ₁ b ₃ . . . b _(N-1)for i=1 . . . N−1si=sq=1if i=index of real(S1) and b ₁=1si=−siif i=index if imag(S1) and b ₁=1sq=−sqend forS2=si·real(S2)+i·sq·imag(S2)  Equation 8

As shown in Equation 8, an XOR operation is performed on each of the bitvalues allocated to the real number part and the imaginary number partof S1 among the input signal S1 and the input signal S2. Then, basedupon the result of the XOR operation, the signs respective to the realnumber part and the imaginary number part of S2 may be decided.Additionally, when transmission signal 1 and transmission 2, whichrespectively correspond to input signal S1 and input signal S2 havingthe MIMO encoding matrix applied thereto, as described above, aretransmitted from transmission antenna 1 and transmission antenna 2, thereception symbols of the reception signal, having passed through thefully correlated channel and being received by the receiver, may havegray mapping. Therefore, the hamming distance between neighboringsymbols within the constellation may not exceed the value of 2.

Since the (M*N)-QAM signal (or (M*M)-QAM signal) received by thereceiving end has a minimum (or uniform) Euclidean distance and graymapping, in case of the second embodiment of the present invention, thesame performance of the SIMO method may also be expected in the fullycorrelated MIMO channel. However, when the ML decoder decodes thereception signal and acquired S1 and S2, since the S2 value depends uponS1, the complexity level may be increased. And, in an un-correlated MIMOchannel, the performance is likely to be degraded due to a correlationbetween the input signals.

3. Third Embodiment MIMO Encoding Method Determining an MIMO EncodingParameter while Considering a Hamming Distance in Addition to aEuclidean Distance

The third embodiment of the present invention proposes a method ofperforming MIMO encoding by determining a value a, so that the overallconstellation of the reception signal does not have a minimum Euclideandistance, as in the first embodiment of the present invention, and sothat the Euclidean distance can be optimized based upon a hammingdistance of the reception signal.

That is, in the third embodiment, the Euclidean distance is beingadjusted in order to compensate a difference in the recovery performancerespective to a difference in the hamming distance with a difference inthe power level. More specifically, with respect to neighboring symbols,wherein a difference in the number of bits of one symbol is 2 times thatof another symbol, a performance degradation respective to a differencein the hamming distance, which may occur during the reception signalrecovery, may be compensated by adjusting (i.e., increasing) theEuclidean distance, so that the section having 2 times the hammingdistance can be provided with greater power level. First of all, arelative Euclidean distance is determined with respect to a receptionsignal, which corresponds to a combination of the 2 transmission signals(St1, St2) both being received by the receiving end. Referring to theabove-described Equation 3, it will be apparent that the minimumEuclidean distance of a 16-QAM symbol having a decreasing power level isequal to 2(a−1), and that the minimum Euclidean distance of a 16-QAMsymbol having an increasing power level is equal to 2(a+1) (this isbecause one reception signal is expressed as R=h{(a+1)S1+(a−1)S2}).

In the third embodiment, the MIMO encoder uses the above-described MIMOmatrix in order to perform MIMO encoding, so that each input signal canbe assigned with a different power level, and so that each input signalcan have a different Euclidean distance. That is, according to the thirdembodiment of the present invention, the MIMO encoder may calculate anddetermine the value of an encoding parameter a, so that input signalsbeing assigned with different power levels can each have a Euclideandistance, which can compensate for the difference in the hammingdistance. Thus, the MIMO encoding process may be performed. Moreover,such value of a may be represented as Equation 9 shown below, accordingto a combination of the modulation methods.

$\begin{matrix}{a = \left\{ \begin{matrix}{\sqrt{2} + 1} & {{{for}\mspace{14mu}{QPSK}} + {QPSK}} \\{{\left( {\sqrt{2} + 3 + \sqrt{5}} \right)\text{/}\left( {\sqrt{2} + 3 - \sqrt{5}} \right)},} & {{{for}\mspace{14mu}{QPSK}} + {16{QAM}}} \\{{\left( {\sqrt{2} + 4} \right)\text{/}\left( {\sqrt{2} + 2} \right)},} & {{{for}\mspace{14mu} 16{QAM}} + {16{QAM}}}\end{matrix} \right.} & {{Equation}\mspace{14mu} 9}\end{matrix}$

In case of QPSK+16QAM MIMO, it will be assumed that the value proposedabove corresponds to when the constellation mapper has performednormalization of the power level to 1, after performing QAM modulationon input signal S1 and input signal S2 by respectively using QPSK and16QAM. In case the normalization process is not performed, the value amay be corrected accordingly.

Additionally, in addition to the value proposed in the case ofQPSK+16QAM MIMO, a value of 4.0 may be used as the value a. In case ofQPSK+16QAM MIMO, this is due to the characteristic enabling the combinedsignal to express both S1 and S2, even in a case of using the SM methodin the fully correlated channel. In this case, in order to compensatefor the performance in a high coding rate of an outer code, a valueproximate to 4.0 may be used instead of the value calculated by usingEquation 9.

Based upon the description presented above, when comparing the secondembodiment of the present invention with the third embodiment of thepresent invention, in the fully correlated MIMO channel, the secondembodiment of the present invention shows a performance identical tothat of the SIMO, thereby causing no loss in the performance.Accordingly, the disadvantages of the MIMO method of the fullycorrelated MIMO channel may be enhanced. However, according to thesecond embodiment of the present invention, due to the MIMO encodingprocess, since the input data S1 and S2 are not independent from oneanother, the input data S2 may vary in accordance with the input dataS1, thereby causing degradation in the performance in an un-relatedchannel. Therefore, the reception of S1 and any decoding error occurringduring the reception of S1 may be reflected to S2, thereby causingadditional decoding error in S2. In order to resolve such problem, thepresent invention may use an iterative ML detection process.

The iterative ML detection includes an outer code in an iterative loop.Then, the iterative ML detection process uses a soft posterioriprobability value of S1, which is outputted from the outer code, as apriori probability value of the ML detector. Accordingly, by reducingany detection error, any possible application of the detection error ofS1 to the S2 detection may be reduced. By using this method, when usingthe MIMO encoding method according to the second embodiment of thepresent invention, the fully correlated MIMO channel may show theperformance of an SIMO system, and the un-correlated MIMO channel mayshow the performance of the SM method.

The MIMO encoding process according to the third embodiment of thepresent invention is devised and designed so that the reception signalbeing received through the fully correlated MIMO channel can considerboth the hamming distance and the Euclidean distance. Accordingly, thethird embodiment of the present invention shows an excellent performancein the fully correlated MIMO channel. And, in comparison with the SMmethod, since the MIMO encoding process according to the thirdembodiment of the present invention shows no loss in performance in theun-correlated MIMO channel, it is verified that the gain in both theMIMO transmission and the MIMO reception can be used. In this case,since the complexity level of the receiver is similar to the complexitylevel corresponding to the SM method, the MIMO encoding processaccording to the third embodiment of the present invention is alsoadvantageous in implementing the receiver of the present invention.

Additionally, the demuxes (131300-0, 131300-1, 132300) within the BICMmodule of FIG. 17 may position the data, so that a difference inrobustness, which occurs after a symbol mapping process, can be reduced,and may decide a number of bits being transmitted for each carrier. Forsimplicity in the description of the present invention, the demuxes(131300-0, 131300-1, 132300) will be referred to as bit-cell demuxes.The bit-cell demuxes of the present invention are used for adequatelypositioning different reliability levels, which are generated whenperforming QAM modulation, in an LDPC codeword, so as to optimize theerror correction capability of the LDPC.

As an error correcting coding method for transmitting information byreducing the likelihood of information loss to a minimum level, the LDPCcoding corresponds to a linear error correcting code. An LDPC block maybe expressed as parameters being expressed as N and K. Herein, Nrepresents a block length (# bit), and K indicates a number of encodedinformation bits included in an LDPC block. A data size (or data amount)that can be transmitted by an LDPC block may be decided in accordancewith the size of an LDPC parity region and a code rate.

The code rate that can be applied in the present invention maycorrespond to any one of 1/4, 2/5, 3/5, 1/2, 4/5, 1/3, 2/3, 3/4, 5/6.And, the length of an LDPC block may correspond to any one of 16200 bits(or also referred to as 16K) and 64800 bits (or also referred to as64K).

More specifically, an LDPC codeword bit being outputted from the FECencoder may be inputted to the bit interleaver, and the bit interleavermay perform bit-unit interleaving on the inputted LDPC codeword bitwithin the LDPC block, thereby outputting the interleaved LDPC codewordbit to the bit-cell demux. The bit-cell demux divides thebit-interleaved and inputted LDPC codeword bit stream into a pluralityof bit streams. For example, when the LDPC block length is equal to16800, the LDPC codeword bit stream may be divided into 2 bit streamswhen the modulation format that is to be used for the symbol mappingprocess corresponds to QPSK, 8 bit streams when the modulation formatcorresponds to 16QAM, 12 bit streams when the modulation formatcorresponds to 64QAM, and 8 bit streams when the modulation formatcorresponds to 256QAM. More specifically, when the LDPC block length isequal to 16800, and when the modulation format that is to be used forthe symbol mapping process corresponds to QPSK, the number ofsub-streams is equal to 2, when the modulation format corresponds to16QAM, the number of sub-streams is equal to 8, when the modulationformat corresponds to 64QAM, the number of sub-streams is equal to 12,and when the modulation format corresponds to 256QAM, the number ofsub-streams is equal to 8. When the modulation format corresponds to256QAM, the 8 bits may become one bit group.

At this point, an order of output from the bit-cell demux may varydepending upon a predetermined condition or a reliability positioningmethod. More specifically, the output order of the bits being outputtedfrom the bit-cell demux may vary in accordance with reliabilitypositioning, a code rate, and a modulation method, which are indicatedwhen the corresponding bit group is mapped to a QAM symbol.

In other words, demultiplexing refers to mapping a bit-interleaved inputbit v_(di) to an output bit b_(e,do).

Herein, do represents di div Nsubstreams, e signifies a number of ademultiplexed bit stream (0≦e<N_(substreams)), and variations may occurin accordance with a di value.

v_(di) represents an input of the bit-cell demux, and di corresponds toan input bit number. b_(e,do) represents an output of the bit-celldemux, and do corresponds to a bit number of a given stream in an outputof the bit-cell demux.

(a) to (e) of FIG. 20 illustrate exemplary output orders of the bit-celldemux in accordance to each code rate, when an LDPC block length isequal to 16800, and when the modulation format that is to be used forsymbol mapping correspond to 256QAM. When the modulation formatcorresponds to 256QAM, an 8-bit unit may be mapped to one symbol.

(a) of FIG. 20 shows an output order of the bit-cell demux, when thecode rate is 1/4, and the demux method shown in (a) of FIG. 20 will bereferred to as 256QAM Type 1-1. More specifically, in case of Type 1-1,when the bit-interleaved input bits are inputted to the bit-cell demuxby the order of 0,1,2,3,4,5,6,7, the bits being outputted from thebit-cell demux may be outputted by the output order of 5,3,2,7,1,6,4,0.Then, the constellation mapper may perform symbol mapping by the orderof output outputted from the bit-cell demux. In this case, a reliabilityalignment of C,B,B,D,A,D,C,A starting from the first bit to the last bitof the LDPC codeword may be obtained. A,B,C,D collectively indicate thereliability when bits of the corresponding bit group are mapped to a QAMsymbol. Herein, the order of high reliability is ranked by the order ofA>B>C>D.

(b) of FIG. 20 shows an output order of the bit-cell demux, when thecode rate is 2/5 and 3/5, and the demux method shown in (b) of FIG. 20will be referred to as 256QAM Type 1-2. More specifically, in case ofType 1-2, when the bit-interleaved input bits are inputted to thebit-cell demux by the order of 0,1,2,3,4,5,6,7, the bits being outputtedfrom the bit-cell demux may be outputted by the output order of5,1,0,7,3,6,4,2. Then, the constellation mapper may perform symbolmapping by the order of output outputted from the bit-cell demux. Inthis case, a reliability alignment of C,A,A,D,B,D,C,B starting from thefirst bit to the last bit of the LDPC codeword may be obtained.

(c) of FIG. 20 shows an output order of the bit-cell demux, when thecode rate is 1/2, and the demux method shown in (c) of FIG. 20 will bereferred to as 256QAM Type 1-3. More specifically, in case of Type 1-3,when the bit-interleaved input bits are inputted to the bit-cell demuxby the order of 0,1,2,3,4,5,6,7, the bits being outputted from thebit-cell demux may be outputted by the output order of 7,3,1,6,5,2,4,0.Then, the constellation mapper may perform symbol mapping by the orderof output outputted from the bit-cell demux. In this case, a reliabilityalignment of D,B,A,D,C,B,C,A starting from the first bit to the last bitof the LDPC codeword may be obtained.

(d) of FIG. 20 shows an output order of the bit-cell demux, when thecode rate is 4/5, and the demux method shown in (d) of FIG. 20 will bereferred to as 256QAM Type 1-4. More specifically, in case of Type 1-4,when the bit-interleaved input bits are inputted to the bit-cell demuxby the order of 0,1,2,3,4,5,6,7, the bits being outputted from thebit-cell demux may be outputted by the output order of 3,2,1,5,7,6,4,0.Then, the constellation mapper may perform symbol mapping by the orderof output outputted from the bit-cell demux. In this case, a reliabilityalignment of B,B,A,C,D,D,C,A starting from the first bit to the last bitof the LDPC codeword may be obtained.

(e) of FIG. 20 shows an output order of the bit-cell demux, when thecode rate is 1/3. 2/3, 3/4, 5/6, and the demux method shown in (e) ofFIG. 20 will be referred to as 256QAM Type 1-5. More specifically, incase of Type 1-5, when the bit-interleaved input bits are inputted tothe bit-cell demux by the order of 0,1,2,3,4,5,6,7, the bits beingoutputted from the bit-cell demux may be outputted by the output orderof 7,3,1,5,2,6,4,0. Then, the constellation mapper may perform symbolmapping by the order of output outputted from the bit-cell demux. Inthis case, a reliability alignment of D,B,A,C,B,D,C,A starting from thefirst bit to the last bit of the LDPC codeword may be obtained.

FIG. 21 illustrates exemplary mapping correlation between the input bitsand the output bits of the bit-cell demux according demux type of FIG.20.

In case of 256QAM, 8 bits are mapped to one QAM symbol. At this point,among (b0, b1, b2, b3, b4, b5, b6, b7), which correspond to the QAMsymbol bits, bits b0, b2, b4, b6 may decide the code and size of thereal number part, and bits b1, b3, b5, b7 may decide the code and sizeof the imaginary number part. More specifically, bits b0 and b1 mayrespectively decide the code of the real number part and the imaginarynumber part, and bits b2, b3, b4, b5, b6, b7 may respectively decide thesize of the real number part and the imaginary number part. Since it iseasier to determine the code than to determine the size of the modulatedsymbol, bits b0 and b1, which correspond to the 2 bits located in theMSB, have the highest reliability, and bits b6 and b7, which correspondto the 2 bits located in the LSB, have the lowest reliability.

If the bit-cell demux operates as 256QAM Type 1-1, by using the bitrealignment of the bit-cell demux, in the constellation mapper, the lastbit (v7) within a sub-stream may be allocated to a code bit (b0,0) ofthe real number part, and the 5^(th) bit (v4) may be allocated to a codebit (b1,0) of the imaginary number part. Additionally, the 3^(rd),7^(th), and 6^(th) bits (v2,v6,v5) are sequentially allocated to thesize bits (b2,0,b4,0,b6,0) of the real number part, and the 2^(nd),1^(st), and 4^(th) bits (v1,v0,v3) are sequentially allocated to thesize bits (b3,0,b5,0,b7,0) of the imaginary number part.

For the remaining types, i.e., Type 1-2 to Type 1-5, since reference maybe made to the description of Type 1-1, detailed description of the samewill be omitted herein.

(a) to (c) of FIG. 22 illustrate other exemplary output orders of thebit-cell demux in accordance to each code rate, when an LDPC blocklength is equal to 16800, and when the modulation format that is to beused for symbol mapping correspond to 256QAM.

(a) of FIG. 22 shows an output order of the bit-cell demux, when thecode rate is 1/4, 1/3, 2/5, 3/5, and the demux method shown in (a) ofFIG. 22 will be referred to as 256QAM Type 2-1. More specifically, incase of Type 2-1, when the bit-interleaved input bits are inputted tothe bit-cell demux by the order of 0,1,2,3,4,5,6,7, the bits beingoutputted from the bit-cell demux may be outputted by the output orderof 5,1,3,7,0,6,4,2. Then, the constellation mapper may perform symbolmapping by the order of output outputted from the bit-cell demux. Inthis case, a reliability alignment of C,A,B,D,A,D,C,B starting from thefirst bit to the last bit of the LDPC codeword may be obtained.

(b) of FIG. 22 shows an output order of the bit-cell demux, when thecode rate is 1/2, 2/3, 4/5, and the demux method shown in (b) of FIG. 22will be referred to as 256QAM Type 2-2. More specifically, in case ofType 2-2, when the bit-interleaved input bits are inputted to thebit-cell demux by the order of 0,1,2,3,4,5,6,7, the bits being outputtedfrom the bit-cell demux may be outputted by the output order of7,3,1,6,2,5,4,0. Then, the constellation mapper may perform symbolmapping by the order of output outputted from the bit-cell demux. Inthis case, a reliability alignment of D,B,A,D,B,C,C,A starting from thefirst bit to the last bit of the LDPC codeword may be obtained.

(c) of FIG. 22 shows an output order of the bit-cell demux, when thecode rate is 1/4, 1/3, 2/3, 4/5, 3/4, 5/6, and the demux method shown in(c) of FIG. 22 will be referred to as 256QAM Type 2-3. Morespecifically, in case of Type 2-3, when the bit-interleaved input bitsare inputted to the bit-cell demux by the order of 0,1,2,3,4,5,6,7, thebits being outputted from the bit-cell demux may be outputted by theoutput order of 7,3,1,5,2,6,4,0. Then, the constellation mapper mayperform symbol mapping by the order of output outputted from thebit-cell demux. In this case, a reliability alignment of D,B,A,C,B,D,C,Astarting from the first bit to the last bit of the LDPC codeword may beobtained.

In FIG. 22, when the code rate is 1/4, 1/3, the bit-cell demux of Type2-1 or Type 2-3 may both be used. Similarly, when the code rate is 2/3,4/5, the bit-cell demux of Type 2-2 or Type 2-3 may both be used.

Additionally, when performing reliability alignment as shown in FIG. 22,since the number of bit-cell demuxes may be reduced to a smaller numberas compared to FIG. 20, the system complexity may be reduced.

FIG. 23 illustrates exemplary mapping correlation between the input bitsand the output bits of the bit-cell demux according demux type of FIG.22.

If the bit-cell demux operates as 256QAM Type 2-1, by using the bitrealignment of the bit-cell demux, in the constellation mapper, the5^(th) bit (v4) within a sub-stream may be allocated to a code bit(b0,0) of the real number part, and the 2^(nd) bit (v1) may be allocatedto a code bit (b1,0) of the imaginary number part. Additionally, the8^(th), 7^(th), and 6^(th) bits (v7,v6,v5) are sequentially allocated tothe size bits (b2,0,b4,0,b6,0) of the real number part, and the 3^(rd),1^(st), and 4^(th) bits (v2,v0,v3) are sequentially allocated to thesize bits (b3,0,b5,0,b7,0) of the imaginary number part.

For the remaining types, i.e., Type 2-2 and Type 2-3, since referencemay be made to the description of Type 2-1, detailed description of thesame will be omitted herein.

(a) to (c) of FIG. 24 illustrate other exemplary output orders of thebit-cell demux in accordance to each code rate, when an LDPC blocklength is equal to 16800, and when the modulation format that is to beused for symbol mapping correspond to 256QAM.

(a) of FIG. 24 shows an output order of the bit-cell demux, when thecode rate is 2/5, 3/5, and the demux method shown in (a) of FIG. 24 willbe referred to as 256QAM Type 3-1. More specifically, in case of Type3-1, when the bit-interleaved input bits are inputted to the bit-celldemux by the order of 0,1,2,3,4,5,6,7, the bits being outputted from thebit-cell demux may be outputted by the output order of 5,1,0,7,3,6,4,2.Then, the constellation mapper may perform symbol mapping by the orderof output outputted from the bit-cell demux. In this case, a reliabilityalignment of C,A,A,D,B,D,C,B starting from the first bit to the last bitof the LDPC codeword may be obtained.

(b) of FIG. 24 shows an output order of the bit-cell demux, when thecode rate is 1/2, and the demux method shown in (b) of FIG. 24 will bereferred to as 256QAM Type 3-2. More specifically, in case of Type 3-2,when the bit-interleaved input bits are inputted to the bit-cell demuxby the order of 0,1,2,3,4,5,6,7, the bits being outputted from thebit-cell demux may be outputted by the output order of 7,3,1,6,5,2,4,0.Then, the constellation mapper may perform symbol mapping by the orderof output outputted from the bit-cell demux. In this case, a reliabilityalignment of D,B,A,D,C,B,C,A starting from the first bit to the last bitof the LDPC codeword may be obtained.

(c) of FIG. 24 shows an output order of the bit-cell demux, when thecode rate is 1/4, 1/3, 2/3, 4/5, 3/4, 5/6, and the demux method shown in(c) of FIG. 24 will be referred to as 256QAM Type 3-3. Herein, Type 3-3performs demultiplexing by using the same method as Type 2-3. Therefore,Type 3-3 may also be referred to as Type 2-3.

Additionally, when performing reliability alignment as shown in FIG. 24,since the number of bit-cell demuxes may be reduced to a smaller numberas compared to FIG. 20, the system complexity may be reduced.

(a) to (e) of FIG. 25 illustrate exemplary output orders of the bit-celldemux in accordance to each code rate, when an LDPC block length isequal to 16800, and when the modulation format that is to be used forsymbol mapping correspond to 64QAM. When the modulation formatcorresponds to 64QAM, a 6-bit unit may be mapped to one symbol.

(a) of FIG. 25 shows an output order of the bit-cell demux, when thecode rate is 2/5, 3/5, and the demux method shown in (a) of FIG. 25 willbe referred to as 64QAM Type 2-1. More specifically, in case of 64QAMType 2-1, when the bit-interleaved input bits are inputted to thebit-cell demux by the order of 0,1,2,3,4,5,6,7,8,9,10,11, the bits beingoutputted from the bit-cell demux may be outputted by the output orderof 5,6,1,7,9,11,3,8,10,4,2,0. Then, the constellation mapper may performsymbol mapping by the order of output outputted from the bit-cell demux.In this case, a reliability alignment of C,A,A,A,B,C,B,B,C,C,B,Astarting from the first bit to the last bit of the LDPC codeword may beobtained. Herein, the order of high reliability is ranked by the orderof A>B>C>D.

(b) of FIG. 25 shows an output order of the bit-cell demux, when thecode rate is 1/2, and the demux method shown in (b) of FIG. 25 will bereferred to as 64QAM Type 2-2. More specifically, in case of 64QAM Type2-2, when the bit-interleaved input bits are inputted to the bit-celldemux by the order of 0,1,2,3,4,5,6,7,8,9,10,11, the bits beingoutputted from the bit-cell demux may be outputted by the output orderof 5,11,7,1,8,10,4,9,6,2,3,0. Then, the constellation mapper may performsymbol mapping by the order of output outputted from the bit-cell demux.In this case, a reliability alignment of C,C,A,A,B,C,C,B,A,B,B,Astarting from the first bit to the last bit of the LDPC codeword may beobtained.

(c) of FIG. 25 shows an output order of the bit-cell demux, when thecode rate is 1/4, 1/3, 2/3, 4/5, 3/4, 5/6, and the demux method shown in(c) of FIG. 25 will be referred to as 64QAM Type 2-3. More specifically,in case of 64QAM Type 2-3, when the bit-interleaved input bits areinputted to the bit-cell demux by the order of0,1,2,3,4,5,6,7,8,9,10,11, the bits being outputted from the bit-celldemux may be outputted by the output order of 11,7,3,10,6,2,9,5,1,8,4,0.Then, the constellation mapper may perform symbol mapping by the orderof output outputted from the bit-cell demux. In this case, a reliabilityalignment of C,A,B,C,A,B,B,C,A,B,C,A starting from the first bit to thelast bit of the LDPC codeword may be obtained.

(a), (b) of FIG. 26 illustrate exemplary output orders of the bit-celldemux in accordance to each code rate, when an LDPC block length isequal to 16800, and when the modulation format that is to be used forsymbol mapping correspond to 16QAM.

(a) of FIG. 26 shows an output order of the bit-cell demux, when thecode rate is 1/2, and the demux method shown in (a) of FIG. 26 will bereferred to as 16QAM Type 2-2. More specifically, in case of 16QAM Type2-2, when the bit-interleaved input bits are inputted to the bit-celldemux by the order of 0,1,2,3,4,5,6,7, the bits being outputted from thebit-cell demux may be outputted by the output order of 3,1,5,7,6,4,2,0.Then, the constellation mapper may perform symbol mapping by the orderof output outputted from the bit-cell demux. In this case, a reliabilityalignment of B,A,A,B,B,A,B,A starting from the first bit to the last bitof the LDPC codeword may be obtained.

(b) of FIG. 26 shows an output order of the bit-cell demux, when thecode rate is 1/4, 1/3, 2/5, 3/5, 2/3, 4/5, 3/4, 5/6, and the demuxmethod shown in (b) of FIG. 26 will be referred to as 16QAM Type 2-3.More specifically, in case of 16QAM Type 2-3, when the bit-interleavedinput bits are inputted to the bit-cell demux by the order of0,1,2,3,4,5,6,7, the bits being outputted from the bit-cell demux may beoutputted by the output order of 7,1,4,2,5,3,6,0. Then, theconstellation mapper may perform symbol mapping by the order of outputoutputted from the bit-cell demux. In this case, a reliability alignmentof B,A,A,B,A,B,B,A starting from the first bit to the last bit of theLDPC codeword may be obtained.

As described above, the demux type may vary depending upon, for example,a symbol mapping method or a code rate of error correction encoding. Inother words, another demux type may be used in accordance with thedifferent symbol mapping methods, code rates, and reliability alignment.

Moreover, for bit positions having the same reliability, even if theorder of the bit positions is changed, the same effect may be gained.Accordingly, any bit alignment may be included in the structure of thebit-cell demux according to the present invention, as long as the bitalignment satisfies the conditions of the reliability alignment shown inFIG. 20 to FIG. 26.

As described above, when bit re-alignment is performed in the bit-celldemux in accordance with the modulation format and the code rate, andwhen symbol mapping is performed in the constellation mapper inaccordance with the modulation formation, a transmitted signal mayacquire the initial alignment of the LDPC codeword from the receiver ofthe cell-bit mux, thereby being transmitted to the FRC decoder.

Thus, an optimal error correction performance of the LDPC may be gainedeven at a lower code rate for a mobile service or a service in alocation having a weaker signal, such as an indoor location. Morespecifically, by performing bit re-alignment and symbol mapping of theLDPC codeword through the reliability alignment as shown in FIG. 20 toFIG. 26, the present invention may gain more enhanced robustness whileensuring commonality with the conventional broadcasting/communicationsystem.

FIG. 27 illustrates a block diagram showing an exemplary structure of abroadcast signal receiving apparatus according to an embodiment of thepresent invention.

The broadcast signal receiving apparatus according to the presentinvention may include an OFDM demodulator (138100), a frame demapper(138200), a BICM decoder (138300), and an output processor (138400).

The frame demapper (138200) may also be referred to as a frame parser.

The OFDM demodulator (138100) converts time domain signals to frequencydomain signals. Herein, the time domain signals correspond to signalsbeing received through multiple reception antennae and then beingconverted to digital signals. Among the signals being converted tofrequency domain signals, the frame demapper (138200) outputs the PLPsdesignated to required services. The BICM decider (138300) correctserrors that occur due to the transmission channel, and the outputprocessor (138300) performs procedures required for generating an outputTS or IP or GS stream.

FIG. 28 illustrates a block diagram showing an exemplary structure of anOFDM demodulator (131800) of the broadcast signal receiving apparatus.More specifically, the OFDM demodulator of FIG. 28 performs an inverseprocess of the OFDM generator of FIG. 19. According to the embodiment ofthe present invention, in order to receive a broadcast signal, which istransmitted by using a MIMO or MISO, two reception antennae (Rx1, Rx2)are used. An embodiment according to the present invention accordinguses a polarity multiplexing MIMO method.

The OFDM demodulator (138100) of FIG. 28 includes a first receiving unitconfigured to perform OFDM demodulation on a signal, which is receivedthrough the first reception antenna (Rx1), and a second receiving unitconfigured to perform OFDM demodulation on a signal, which is receivedthrough the second reception antenna (Rx2). The first receiving unit mayinclude a tuner (139000-0), an ADC (139100-0), a P1 symbol detector(139200-0), an AP1 symbol detector (139250-0), a time/frequencysynchronization unit (139300-0), a GI remover (139400-0), an FFT module(139500-0), and a channel estimator (139600-0). And, the secondreceiving unit may include a tuner (139000-1), an ADC (139100-1), a P1symbol detector (139200-1), an AP1 symbol detector (139250-1), atime/frequency synchronization unit (139300-1), a GI remover (139400-1),an FFT module (139500-1), and a channel estimator (139600-1). The OFDMdemodulator further includes an MISO decoder (139700) at a outputterminal of the first and second receiving unit. The MISO (139700) willbe referred to as an MISO processor. The description of the presentinvention will be mostly made based upon the blocks included in thefirst receiving unit. And, since the operations of the blocks includedin the second receiving unit are identical to those of the blocksincluded in the first receiving unit, the detailed description of thesame will be omitted for simplicity.

The tuner (139000-0) of the first receiving unit may select only asignal of a desired (or wanted) frequency band. Also, according to theembodiment of the present invention, in order to be applied to the TFSsystem, the tuner (139000-0) may have an FH (Frequency Hopping)function. The ADC (139100-0) converts the analog broadcasting signal,which is inputted through a first path (e.g., V-path), to a digitalbroadcasting signal.

The P1 symbol detector (139200-0) detects a P1 symbol from the digitalbroadcast signal, and the P1 symbol detector (139200-0) then uses P1signaling information, which is carried by the P1 symbol, so as todetermine the frame structure of the currently received signal. The AP1symbol detector (139250-0) may detect and decode an AP1 symbol, whichtransmits the AP1 signaling information included in the digitalbroadcasting signal, so as to gain pilot pattern information of thecurrent signal frame. Herein, the detection and decoding of the P1symbol and the AP1 symbol may be performed by the P1 symbol detector(139200-0), and, in this case, the AP1 symbol detector (139250-0) may beomitted.

The time/frequency synchronization unit (139300-0) uses at least one ofthe P1 signaling information and the AP1 signaling information so as toperform GI extraction and time synchronization and carrier frequencysynchronization.

The GI remover (139400-0) removes the GI from the synchronized signal,and the FFT module (139500-0) converts the GI-removed signal to afrequency domain signal.

The channel estimator (139600-0) uses a pilot signal being inserted inthe frequency domain signal, so as to estimate a transmission channelstarting from a transmission antenna to a reception antenna. The channelestimator (139600-0) performs channel equalization compensating for adistortion in a transmission channel based on the estimated transmissionchannel. The channel equalization is optional. The MISO decoder (139700)performs MISO decoding on data outputted from the channel estimator(139600-0).

When MISO decoding is performed on MISO PLP data and L1 signaling data,the MISO decoder (139700) of the present invention may perform 4different operations. Each operation will hereinafter be described.

First of all, when the channel estimators (139600-0,139600-1) includedin the first receiving unit and the second receiving unit do not performchannel equalization on the MISO PLP, the MISO decoder (139700) mayapply a channel estimation effect on all reference points that can betransmitted, thereby being capable of calculating the LLR value.Accordingly, the same effect as channel equalization may be gained.

Secondly, the MISO decoder (139700) may perform the following operationsin accordance with the operations of the constellation mapper, which isincluded in the BICM module of the broadcasting signal transmitter. Forexample, when the constellation of the constellation map is rotated by apredetermined angle, and when only the Q-phase element of theconstellation is delayed by an arbitrary value, the MISO decoder(139700) may delay only the I-phase element of the constellation by anarbitrary value and may calculate the 2D-LLR value based upon theconstellation rotation angle.

According to another embodiment of the present invention, when theconstellation mapper does not rotate the constellation, and when onlythe Q-phase element of the constellation is not delayed by the arbitraryvalue, the MISO decoder (139700) may be capable of calculating the2D-LLR value based upon a normal QAM.

Thirdly, the MISO decoder (139700) may select a MISO decoding matrix, sothat an inverse process of the MISO encoder, which is included in theOFDM generator described in FIG. 19, can be performed in accordance withthe MISO encoding matrix used by the MISO encoder. And, then, the MISOdecoder (139700) may perform MISO decoding.

Finally, the MISO decoder (139700) may merge the MISO PLP data, whichare received through 2 reception antennae. The signal merging methodaccording to the present invention may include maximum ratio combining,equal gain combining, selective combining, and so on. In this case, theMISO decoder (139700) may maximize the SNR of the merged signal, so asto gain a diversity effect.

Additionally, the MISO decoder (139700) may perform MISO decoding on asignal, which is processed with signal merging. Then, after performingMISO decoding on the input of the two antennae, the MISO decoder(139700) may merge the MISO decoded signals.

The MISO decoder (139700) may perform MIMO decoding on the MIMO PLPdata, which are being inputted through the first path and the secondpath. In this case, the MISO decoder (139700) may perform the sameoperations as the above-described MISO decoding process. However, amongthe 4 operation steps, the last operation, i.e., the signal mergingoperation may not be performed.

FIG. 29 illustrates an exemplary structure of any one of the P1 symboldetectors (139200-0, 139200-1) according to an embodiment of the presentinvention. Herein, the P1 symbol detectors (139200-0, 139200-1) may alsobe referred to as a C-A-B preamble detector.

The present invention will describe the P1 symbol detector (139200-0) ofthe first receiving unit. An operation description of the P1 symboldetector (139200-1) of the second receiving unit refers to that of theP1 symbol detector (139200-0) of the first receiving unit.

More specifically, the signal that is converted to a digital signal fromthe ADC (139100-0) may be inputted to a down shifter (139801), a 1^(st)conjugator (139803), and a 2^(nd) delayer (139806) of the P1 symboldetector (139200).

The down shifter (139801) performs inverse modulation by multiplying

𝕖^(−j 2π f_(SH^(t)))by the input signal. When inverse modulation is performed by the downshifter (139801), the signal being frequency-shifted and inputted isrecovered to the original signal. The inverse modulated signal may beoutputted to a 1^(st) delayer (139802) and a 2^(nd) conjugator (139807).

The 1^(st) delayer (139802) delays the inverse-modulated signal by alength of part C (T_(C)) and then outputs the delayed signal to the1^(st) conjugator (139803). The 1^(st) conjugator (139803) performscomplex-conjugation on the signal, which is delayed by a length of partC (T_(C)). Then, the 1^(st) conjugator (139803) multiplies the inputsignal by the complex-conjugated signal, thereby outputting theprocessed signal to a 1^(st) filter (139804). The 1^(st) filter (139804)uses a running average filter having the length of T_(R)=T_(A), so as toremove (or eliminate) any excessively and unnecessarily remainingmodulation elements, thereby outputting the processed signal to a 3^(rd)delayer (139805). The 3^(rd) delayer (139805) delays the filtered signalby a length of part A (i.e., effective (or valid) symbol) (T_(A)), so asto output the delayed signal to a multiplier (139809).

The 2^(nd) delayer (139806) delays the input signal by a length of partB (T_(B)) and then outputs the delayed signal to the 2^(nd) conjugator(139807). The 2^(nd) conjugator (139807) performs complex-conjugation onthe signal, which is delayed by a length of part B (T_(B)). Then, the2^(nd) conjugator (139807) multiplies the complex-conjugated signal byan inverse-modulated signal, thereby outputting the processed signal toa 2^(nd) filter (139808). The 2^(nd) filter (139808) uses a runningaverage filter having the length of T_(R)=T_(A), so as to remove (oreliminate) any excessively and unnecessarily remaining modulationelements, thereby outputting the processed signal to the multiplier(139809).

The multiplier (139809) multiplies the output of the 2^(nd) filter(139809) by a signal, which is delayed by a length of part A (T_(A)).Thus, a P1 symbol may be detected from each signal frame of the receivedbroadcast signal.

Herein, the length of part C (T_(C)) and the length of part B (T_(B))may be obtained by applying Equation 11 shown above.

FIG. 30 illustrates an exemplary structure of any one of the AP1 symboldetectors (139250-0, 139250-1) according to an embodiment of the presentinvention. Herein, the AP1 symbol detectors (139250-0, 139250-1) mayalso be referred to as an F-D-E preamble detector.

The present invention will describe the AP1 symbol detector (139250-0)of the first receiving unit. An operation description of the AP1 symboldetector (139250-1) of the second receiving unit refers to that of theAP1 symbol detector (139250-0) of the first receiving unit.

More specifically, the signal that is converted to a digital signal fromthe ADC (139100-0) or a signal that is outputted from the P1 symboldetector (139200) may be inputted to an up-shifter (139901), a 1^(st)conjugator (139903), and a 2^(nd) delayer (139906) of the AP1 symboldetector (139250-0).

The up-shifter (139901) performs inverse modulation by multiplying

𝕖^(j 2π f_(SH^(t)))by the input signal. When inverse modulation is performed by theup-shifter (139901), the signal being frequency-shifted and inputted isrecovered to the original signal. More specifically, the up-shifter(139901) of FIG. 30 has the same structure as the down-shifter (139801)of the P1 symbol detector (139200). However, the frequency direction ofeach inverse modulation process is completely opposite to one another.The signal that is inverse modulated by the up-shifter (139901) may beoutputted to a 1^(st) delayer (139902) and a 2^(nd) conjugator (139907).

The 1^(st) delayer (139902) delays the inverse-modulated signal by alength of part F (T_(F)) and then outputs the delayed signal to the1^(st) conjugator (139903). The 1^(st) conjugator (139903) performscomplex-conjugation on the signal, which is delayed by a length of partF (T_(F)). Then, the 1^(st) conjugator (139903) multiplies the inputsignal by the complex-conjugated signal, thereby outputting theprocessed signal to a 1^(st) filter (139904). The 1^(st) filter (139904)uses a running average filter having the length of T_(R)=T_(D), so as toremove (or eliminate) any excessively and unnecessarily remainingmodulation elements, thereby outputting the processed signal to a 3^(rd)delayer (139905). The 3^(rd) delayer (139905) delays the filtered signalby a length of part D (i.e., effective (or valid) symbol) (T_(D)), so asto output the delayed signal to a multiplier (139909).

The 2^(nd) delayer (139906) delays the input signal by a length of partE (T_(E)) and then outputs the delayed signal to the 2^(nd) conjugator(139907). The 2^(nd) conjugator (139907) performs complex-conjugation onthe signal, which is delayed by a length of part E (T_(E)). Then, the2^(nd) conjugator (139907) multiplies the complex-conjugated signal byan inverse-modulated signal, thereby outputting the processed signal toa 2^(nd) filter (139908). The 2^(nd) filter (139908) uses a runningaverage filter having the length of T_(R)=T_(D), so as to remove (oreliminate) any excessively and unnecessarily remaining modulationelements, thereby outputting the processed signal to the multiplier(139909).

The multiplier (139909) multiplies the output of the 2^(nd) filter(139909) by a signal, which is delayed by a length of part D (T_(D)).Thus, an AP1 symbol may be detected from each signal frame of thereceived broadcast signal. Herein, the length of part F (T_(F)) and thelength of part E (T_(E)) may be obtained by applying Equation 11 shownabove.

FIG. 31 illustrates an exemplary frame demapper (138200) of thebroadcasting signal receiving device according to an embodiment of thepresent invention, which is adequate for processing an output of theOFDM demodulator shown in FIG. 28.

According to the embodiment of the present invention, the frame demapper(138200) performs an inverse process of the frame builder (100300) ofthe broadcasting signal transmitting device shown in FIG. 18.

The frame demapper of FIG. 31 may include a first frame demapping block(140100) for processing data being inputted through a first path and asecond frame demapping block (140200) for processing data being inputtedthrough a second path.

The first frame demapping block (140100) may include a first frequencydeinterleaver (140101), a first cell demapper (140102), a first coupler(140103), a second coupler (140104), and a third coupler (140105), andthe second frame demapping block (140200) may include a second frequencydeinterleaver (140201) and a second cell demapper (140202).

Also, the first frequency deinterleaver (140101) and the first celldemapper (140102) and the second frequency deinterleaver (140201) andthe second cell demapper (140202) may perform the same operations withrespect to the first path and the second path or may perform independentoperations.

Hereinafter, a data processing method of the blocks included in a firstframe builder demapping block (140100) and a second frame builderdemapping block (140200) will

be described in detail.

The first frequency deinterleaver (140101) and the second frequencydeinterleaver (140201) may each perform cell unit deinterleaving in afrequency domain on data being inputted through the first path and thesecond path.

The first cell demapper (140102) and the second cell demapper (140202)may extract common PLP data, PLP data, and L1 signaling data from thedeinterleaved data in cell units. The extracted PLP data may includeMISO-decoded MISO PLP data and MIMO-decoded MIMO PLP data, and theextracted L1 signaling data may include information on the currenttransmission frame and the next transmission frame. Furthermore, whensub-slicing has been performed on the PLP data by the transmitter, asub-slicing processor of the first cell demapper (140102) and the secondcell demapper (140202) may merge the sliced PLP data, thereby mergingthe sliced data so as to generate a single stream.

When the MISO decoder of the OFDM modulator does not perform signalcoupling of the MISO-decoded MISO PLP data, the first coupler (140103)may perform signal coupling of the MISO-decoded MISO PLP data.

The second coupler (140104) and the third coupler (140105) perform thesame functions as the first coupler (140103). However, the differenceherein is that the operations are respectively performed on theL1-pre-signaling data and the L1-post-signaling data.

As shown in FIG. 31, data being processed with frame demapping, i.e.,data being outputted through the first path, such as the MISO PLP data,the MIMO PLP data, and the signaling data may be inputted to the BICMdecoder through a path starting from SRx_k to SRx_post, and the MIMO PLPdata being outputted through the second path may be inputted to the BICMdecoder through a path starting from SRx_m+1 to SRx_n+1.

FIG. 32 illustrates an exemplary BICM decoder of the broadcasting signalreceiving device according to an embodiment of the present invention,which is adequate for processing the output of the frame demapper shownin FIG. 31. Most particularly, according to the embodiment of thepresent invention, the BICM decoder performs an inverse process of theMICM module of the broadcasting signal transmitting device shown in FIG.17.

The BICM decoder of FIG. 32 includes a first BICM decoding block(150100) receiving MISO PLP data through one path (SRx_k) and processingthe received data, a second BICM decoding block (150300) receiving MIMOPLP data through two paths (SRx_m, SRx_m+1) and processing the receiveddata, and a third BICM decoding block (150500) receiving L1 signalingdata through two paths (SRx_pre, SRx_post) and processing the receiveddata. Also, the third BICM decoding block (150500) includes a firstdecoding block for processing L1-pre-signaling data and a seconddecoding block for processing L1-post-signaling data

Herein, according to the embodiment of the present invention, the MISOPLP data and the L1 signaling data may be inputted after beingMISO-decoded by the OFDM demodulator of FIG. 31, and the MIMO PLP datamay be MIMO-decoded by the BICM decoder of FIG. 32.

More specifically, the BICM decoder of the present invention mayindependently apply the MISO method on the data being inputted from eachpath, and may also apply the MIMO method.

Hereinafter, the data processing method of each block will be described.

First of all, a first BICM decoding block (150100) may include a timedeinterleaver (150101), a cell deinterleaver (150102), a constellationdemapper (150103), a mux (150104), a bit deinterleaver (150105), and anFEC decoder (150106).

The time deinterleaver (150101) performs deinterleaving in a time domainon the inputted data, which MISO-decoded by the OFDM modulator, so as torecover the data to the initial position, and the cell deinterleaver(150102) may perform cell unit deinterleaving on the time-deinterleaveddata.

The constellation demapper (150103) may perform the following functionsin accordance with the operations of the MISO decoder (139700) of theOFDM demodulator.

First of all, in case the MISO decoder (139700) performs onlyMISO-decoding without directly outputting the LLR value, theconstellation demapper (150103) may calculate the LLR value. Morespecifically, a detailed description will hereinafter be made. Whenconstellation rotation and Q-phase element delay are performed by theconstellation demapper, which is included in the BICM module of thebroadcasting signal transmitting device shown in FIG. 17, theconstellation demapper (150103) may first delay an I-phase element andmay then calculate the LLR value. If the constellation demapper, whichis included in the BICM module of the broadcasting signal transmittingdevice, does not perform constellation rotation and Q-phase elementdelay, the constellation demapper (150103) may calculate an LLR valuebased upon a normal QAM standard.

The method for calculating the LLR value may include a method forcalculating a 2-D LLR and a method for calculating a 1-D LLR value. Incase of calculating the 1-D LLR value, any one of the input to the firstpath and the input to the second path is performed, so as to reduce thecomplexity in the LLR calculation.

The mux (150104) may recover the demapped data to a bit stream format.More specifically, when the output order of the bits are adjusted (orcontrolled) and transmitted from the demux of the transmitting end, themux (150104) recovers the initial output order.

The bit deinterleaver (150105) performs deinterleaving on the inputtedbit stream in bit units, and the FEC decoder (150106) performsFEC-decoding on the data processed with bit-deinterleaving, so as toperform error correction over the transmission channel, therebyoutputting the MISO PLP data. In this case, according to the embodimentof the present invention, LDPC decoding and/or BCH decoding method(s)may be used as the decoding method.

The second BICM decoding block (150300) may include a first timedeinterleaver (150301) and a second time deinterleaver (150401), a firstcell deinterleaver (150302) and a second cell deinterleaver (150402), afirst constellation demapper (150303) and a second constellationdemapper (150403), a mux (150305), a bit deinterleaver (150306), and anFEC decoder (150307).

The first time deinterleaver (150301) and the second time deinterleaver(150401) may perform deinterleaving in a time domain on the inputteddata in cell units, so as to recover data by the initial (or original)data order. In this case, the first cell deinterleaver (150302) and thesecond cell deinterleaver (150402) may perform cell deinterleaving onlyon the data corresponding to half the size of a cell included in an FECblock, among the data being inputted through each path. Eventually, thecell deinterleaving performed by the first cell deinterleaver (150302)and the second cell deinterleaver (150402) may have the same effect asthe deinterleaving performed by the MISO type cell deinterleaver(150102) by using one FEC block.

The MIMO decoder (150303) performs MIMO decoding on the data beingoutputted from the first and second cell deinterleavers (150302,150402). Among the 4 different operations of the MISO decoder (139700),which is included in the ODFM demodulator shown in FIG. 28, the MIMOdecoder (150303) may identically perform the 3 remaining operations ofthe MISO decoder (139700) excluding the fourth operation, i.e., thesignal coupling operation. At this point, the MIMO decoder (150303) mayalso perform decoding by using the MIMO encoding matrix according to thefirst to third embodiments of the present invention.

For the description of the first constellation demapper (150304), thesecond constellation demapper (150404), the mux (150305), the bitdeinterleaver (150306), and the FEC decoder (150307), reference may bemade to the operations of the same blocks included in the first BICMdecoding block (150100).

The third BICM decoding block (150500) includes a first decoding blockfor processing L1-pre-signaling data and a second decoding block forprocessing L1-post-signaling data.

At this point, the L1-pre-signaling data and the L1-post-signaling dataare MISO decoded by the MISO decoder (139700) of the OFDM demodulatorshown in FIG. 28.

The first decoding block may include a time deinterleaver (150501), acell deinterleaver (150502), a constellation demapper (150503), and anFEC decoder (150504), and the second decoding block may include a timedeinterleaver (150601), a cell deinterleaver (150602), a constellationdemapper (150603), a mux (150604), a bit deinterleaver (150605), and anFEC decoder (150606).

Hereinafter, since the functions of each block included in the firstdecoding block and the second decoding block are identical to therespective blocks included in the first BICM decoding block (150100), adetailed description of the same will be omitted. However, according toan embodiment of the present invention, each of the FEC decoders(150504, 150606) shall perform FEC decoding, after performingde-shortening and de-puncturing on the input data.

Eventually, the first BICM decoding block (150100) may output theBICM-decoded MISO PLP data to the output processor, and the second BICMdecoding block (150300) may output the BICM-decoded MIMO PLP data to theoutput processor. Also, the first decoding block of the third BICMdecoding block (150500) may also output the BICM-decodedL1-pre-signaling data to the output processor, and the second decodingblock of the third BICM decoding block (150500) may also output theBICM-decoded L1-post-signaling data to the output processor.

Since the BICM decoder of FIG. 32 is positioned between the first andsecond cell deinterleavers (150302, 150402) and the first and secondconstellation demappers (150304, 150404), by performing MIMO decodingafter performing both the time deinterleaving and cell deinterelavingprocesses is symbol units, the complexity in the memory of thebroadcasting signal recover may be reduced.

According to another embodiment of the present invention, the MIMOdecoder of the second BICM decoding block (150300) may also bepositioned before the first and second time deinterleavers (150301,150401).

FIG. 33 illustrates an exemplary output processor (138300) of thebroadcasting signal receiving device according to an embodiment of thepresent invention.

FIG. 33 shows an exemplary embodiment of the output processor (138300)corresponding to a case when 1 output stream is used (or when 1 PLPinput is used), wherein the output processor (138300) performs theinverse processes of the input processor (100100) and the inputpre-processor (100000).

When 1 output stream is used, the output processor may include a BBdescrambler (190100), a padding remover (190200), a CRC-8 decoder(190300), and a BB frame processor (190400).

The BB descramble (190100) descrambles the inputted bit stream. Morespecifically, the BB descrambler (190100) performs an XOR operation ofthe bit stream, which is identically generated as the PRBS processed bythe BB scrambler (110500) shown in FIG. 14, and an input bit stream,thereby performing descrambling. When required, the padding remover(190200) removes the padding bit, which is inserted by the broadcastingsignal transmitting device. The CRC-8 decoder (190300) performs CRCdecoding on the inputted bit stream, and the BB frame processor mayfirst decode the information included in the BB frame header. Then, theCRC-8 decoder (190300) may use the decoded information, so as to recoverthe TS/IP/GS stream and output the recovered stream.

FIG. 34 illustrates an exemplary output processor (138300) of thebroadcasting signal receiving device according to another embodiment ofthe present invention.

FIG. 34 illustrates an example of an output processor (138300) accordingto an embodiment of the present invention corresponding to a case whenmultiple output streams are used, i.e., when multiple PLPs are received.Herein, the output processor shown herein is similar to the inverseprocess of the input processor (100100) of FIG. 15 and FIG. 16 and theinput pre-processor (100000) of FIG. 7. When components configuring aservice are each received by a different PLP, the output processor(138300) of FIG. 34 is adequate for configuring a single service byextracting the components from each PLP.

The output processor of FIG. 34 may include n+1 number of BBdescramblers (193100-0˜n) for processing n number of PLPs, n+1 number ofpadding removers (193200-0˜n), n+1 number of CRC-8 decoders(193300-0˜n), n+1 number of BB frame processors (193400-0˜n), n+1 numberof De-jitter buffers (193500-0˜n), n+1 number of null packet inserters(193600-0˜n), n−m+1 number of in-band signaling decoders (193700-m˜n), aTS clock regenerator (193800), and a TS re-coupler (193900).

If the output stream corresponds to an IP stream or a GSE stream, theCRC-8 decoders (193300-0˜n) and the n+1 number of null packet inserters(193600-0˜n) may be omitted from the block view of FIG. 34, or thecorresponding blocks may be bypassed. For example, since the IP packetis buffered to best-fit a time stamp, so as to be reproduced by thereceiver, the transmitter is not required to delay the correspondingdata, and a null packet is not required to be added/deleted.

Since the operations of each of the BB descramblers (193100-0˜n), thepadding removers (193200-0˜n), the CRC-8 decoders decoders (193300-0˜n),and the BB frame processors (193400-0˜n) are identical to the operationsof the respective blocks shown in FIG. 33, reference may be made to FIG.33 for the detailed description of the corresponding blocks and,therefore, detailed description of the same will be omitted herein. Inthe description of FIG. 34, only the portions that are different fromthe structure shown in FIG. 33 will be described herein.

The de-jitter buffers (193500-0˜n) compensates for the delays, which arearbitrarily inserted by the transmitting end for the synchronizationbetween the multiple PLPs, in accordance with an TTO (time to outputparameter).

The null packet inserters (193600-0˜n) may refer to DNP (deleted nullpacket) information, which indicate information on the number of deletednull packets, so as to insert the null packets, which are removed by thetransmitting end, in the respective positions of the corresponding TS.At this point, the TS clock regenerator (193800) may recover detailedtime synchronization of the output packet based upon the ISCR (InputStream Time Reference).

The TS coupler (193900) may also be referred to as a TS merger and, asdescribed above, the TS coupler (193900) may recover the common PLP, anddata PLPs, which are recovered as described above, to the initial TS orIP or GSE stream, and may then output the recovered stream. According tothe present invention, TTO, DNP, ISCR information are all included inthe BB frame header and transmitted. The in-band signaling decoders(193700-m˜n) may recover the in-band signaling information, which isbeing transmitted through the data PLP, and may then output therecovered information.

For example, it will be assumed herein that a service is configured of acommon PLP, a video component PLP, an audio component PLP, and datacomponent PLP, as shown in (b) of FIG. 9, through the inputpre-processor (100000) the input processor (100100) of the transmitter.Accordingly, the de-jitter buffers (193500-0˜n) of FIG. 34 may outputmultiple PLPs to the null packet inserters (193600-0˜n), as shown in (b)of FIG. 9, and the null packet inserters (193600-0˜n) may refer to DNPinformation, so as to insert the null packets, which are removed by thetransmitting end, in the respective positions of the corresponding TS.Accordingly, a common TS, a video component TS, an audio component TS,and a data component TS, each having the null packets inserted therein,as shown in (a) of FIG. 9 ((b) of FIG. 8), may be outputted to the TScoupler (193900). When the TS coupler (193900) merges the valid packetsof the common TS, the video component TS, the audio component TS, andthe data component TS, a TS configuring a singled service may beoutputted, as shown in (a) of FIG. 8.

Meanwhile, the output processor of the present invention may furtherinclude an L1 signaling decoder. Additionally, first and second BBdescramblers may further be included in front of the L1 signalingdecoder.

In this case, the first BB descrambler may descramble L1-pre-signalinginformation, which is outputted from the FEC decoder (150504) of thethird BICM decoding module (150500), and the second BB descrambler maydescramble L1-post-signaling information, which is outputted from theFEC decoder (150606) of the third BICM decoding module (150500), therebyoutputting the descrambled information to the L1 signaling decoder. Morespecifically, the first and second BB descramblers may perform XORoperation on a bit stream, which is identically generated as the PRBSbeing processed by the first and second BB scramblers of thetransmitter, and an input bit stream, so as to perform descrambling.

The L1 signaling decoder decodes the descrambled L1-pre-signalinginformation and L1-post-signaling information, so as to recover the L1signaling information. The recovered L1 signaling information includesL1-pre-signaling information and L1-post-signaling information.Additionally, the L1-post-signaling information includes configurableL1-post-signaling information and dynamic L1-post-signaling information.

The L1 signaling information, which is recovered by the L1 signalingdecoder may be delivered to the system controller, so as to provideparameters, which are required by the broadcasting signal receiver forperforming operations, such as BICM (Bit Interleaved Coding andModulation) decoding, frame demapping, OFDM (Orthogonal FrequencyDivision Multiplex) demodulation, and so on.

According to another embodiment of the present invention, instead of theoutput processor, an L1 signaling decoder may also be located at theoutputting end of the FEC decoders (150504,150606) of the third BICMdecoding module (150500), which is included in the BICM decoder 138300).Additionally, a first BB descrambler may be further included between theL1 signaling decoder and the FEC decoder (150504), and a second BBdescrambler may be further included between the L1 signaling decoder andthe FEC decoder (150606). The description on the operations of the firstand second BB descramblers and the L1 signaling decoder is identical tothe description of the corresponding blocks included in the outputprocessor.

FIG. 35 illustrates a block view showing a structure of a broadcastingsignal receiving device according to yet another embodiment of thepresent invention. Herein, FIG. 35 corresponds to a block view showingthe structure of the broadcasting signal receiving device, when thestream type being inputted to the input pre-processor of the transmittercorresponds to the TS format. In case of receiving each of thecomponents configuring a single service through a different PLP, thebroadcasting signal receiving device of FIG. 23 is adequate forextracting the components from each PLP, thereby configuring a singleservice.

In FIG. 35, for the detailed description on the operations of the OFDMdemodulator (210100) and the frame demapper (210200), reference may bemade to the detailed description on the operations of theabove-described OFDM demodulator (138100) and frame demapper (138200),and, therefore, detailed description of the same will be omitted herein.

In FIG. 35, the multiple PLP deinterleaving and demodulator modules(210500), which perform deinterleaving and demodulation on each of themultiple PLPs, perform similar operations as the above-described BICMdecoder (138300). And, multiple BBF decoders and null packetreconstruction modules (210600), which output TS by performing BBF(BaseBand Frame) decoding and null packet reconstruction operations, andthe TS merger (210700) perform operations that are similar to theoperations of the above-described output processor (138400). The L1decoder (210300) corresponds to the above-described L1 signalingdecoder.

In FIG. 35, when a service is selected, the PLP selecting module(210400) controls the frame demapper (210200), so that only the PLP ofthe components configuring the selected service can be outputted fromthe frame demapper (210200). Herein, the service selection may berealized by a user's request, or may be automatically realized in thesystem.

More specifically, the OFDM demodulator (210100) decodes the P1/AP1signaling information, and the L1 decoder (210600) decodes L1/L2signaling information, so as to acquire information on a transmissionframe structure and information on PLP configuration. According to anembodiment of the present invention, the components configuring aservice are received by multiple PLPs. In this case, since PLPinformation or service information on the component structure isincluded in the L1 signaling information, the broadcasting receiver maybe capable of knowing to which PLPs the components, which configure aservice, are included.

Accordingly, when a service is selected, the PLP selecting module(210400) controls the frame demapper (210200), and the frame demapper(210200) outputs multiple sets of PLP data including the correspondingcomponents to the selected service. The multiple sets of PLP data areprocessed with deinterleaving/demodulation processes by thecorresponding deinterleaving and demodulator module. And, after the BBFdecoding/null packet reconstruction processes are processed by the BBFdecoder and null packet reconstruction module, the TS merger (210700)merges the processed data to configure a TS respective to the selectedservice.

For example, it will be assumed herein that a service is configured of acommon PLP, a video component PLP, an audio component PLP, and datacomponent PLP, as shown in (b) of FIG. 9, through the inputpre-processor (100000) the input processor (100100) of the transmitter.Accordingly, the BBF decoders of FIG. 23 may output multiple PLPs to thenull packet reconstruction modules, as shown in (b) of FIG. 9, and thenull packet reconstruction modules may refer to DNP information, so asto insert the null packets, which are removed by the transmitting end,in the respective positions of the corresponding TS. Accordingly, acommon TS, a video component TS, an audio component TS, and a datacomponent TS, each having the null packets inserted therein, as shown in(a) of FIG. 9 ((b) of FIG. 8), may be outputted to the TS merger(210700). When the TS merger (210700) merges the valid packets of thecommon TS, the video component TS, the audio component TS, and the datacomponent TS, a TS configuring a singled service may be outputted, asshown in (a) of FIG. 8.

FIG. 36 illustrates a block view showing a structure of the broadcastingsignal receiving device according to yet another embodiment of thepresent invention. Herein, FIG. 36 corresponds to a block view showingthe structure of the broadcasting signal receiving device, when a streamtype inputted to the input pre-processor of the transmitter correspondto an IP stream format or a GSE stream format. The broadcasting signalreceiving device of FIG. 36 is adequate for configuring a service, byextracting components from each PLP, when the components configuring aservice are included in each PLP.

The broadcasting signal receiving device of FIG. 36 may include an OFDMdemodulator (220100), a frame demapper (220200), an L1 decoder (220300),a PLP selecting module (220400), multiple PLP deinterleaving anddemodulator module (220500), multiple BBF decoder (220600), and a bufferunit (220700). The buffer unit (220700) may include a PSI/SI (IP serviceinformation) buffer, a bootstrap buffer, a metadata buffer, an audiobuffer, a video buffer, and a data buffer depending upon the data type.

For the detailed description on the operations of the OFDM demodulator(220100) and the frame demapper (220200) shown in FIG. 36, reference maybe made to the detailed description on the operations of theabove-described OFDM demodulator (138100) and frame demapper (138200),and, therefore, detailed description of the same will be omitted herein.

The multiple PLP deinterleaving and demodulator module (220500)performing deinterleaving and demodulation on each of the multiple PLPsin FIG. 36 performs operations that are similar to the operations of theabove-described BICM decoder (138300), and the multiple BBF decoders(220600), which perform BBF decoding on each of the multiple PLPs, so asto output an IP stream, also perform operations that are similar to theoperations of the above-described output processor (138400). The L1decoder (220300) corresponds to the above-described L1 signalingdecoder.

In FIG. 36, when a service is selected, the PLP selecting module(220400) controls the frame demapper (220200) so that only the PLPs ofthe components configuring the selected service can be outputted fromthe frame demapper (220200). Herein, the service selection may berealized by a user's request, or may be automatically realized in thesystem.

More specifically, the OFDM demodulator (220100) decodes the P1/AP1signaling information, and the L1 decoder (220600) decodes L1/L2signaling information, so as to acquire information on a transmissionframe structure and information on PLP configuration. According to anembodiment of the present invention, the components configuring aservice are received by multiple PLPs. In this case, since PLPinformation or service information on the component structure isincluded in the L1 signaling information, the broadcasting receiver maybe capable of knowing to which PLPs the components, which configure aservice, are included.

Accordingly, when a service is selected, the PLP selecting module(220400) controls the frame demapper (220200), and the frame demapper(220200) outputs multiple sets of PLP data including the correspondingcomponents to the selected service. The multiple sets of PLP data areprocessed with deinterleaving/demodulation processes by thecorresponding deinterleaving and demodulator module. And, after the BBFdecoding process is processed by the BBF decoder, the processed data areoutputted to the corresponding buffer, among a PSI/SI (IP serviceinformation) buffer, a bootstrap buffer, a metadata buffer, an audiobuffer, a video buffer, and a data buffer of the buffer unit (220700) bya switching process. Then, the PSI/SI (IP service information) buffer,the bootstrap buffer, the metadata buffer, the audio buffer, the videobuffer, and the data buffer may temporarily store PLP data, which areinputted from any one of the multiple BBF decoders (220600), therebyoutputting the stored PLP data. The present invention may furtherinclude a stream merger and a component splitter between the multipleBBF decoders (220600) and the buffer unit (220700).

More specifically, an IP stream of the multiple sets of PLP data, whichare BBF decoded and outputted from the multiple BBF decoders (220600)corresponding to the components of the selected service, after beingprocessed with BBF decoding by the multiple BBF decoders (220600), maybe merged by the stream merger, so as to be outputted as a single IPstream corresponding to the selected service. At this point, the streammerger may refer to an IP address and a UDP port number, so as to mergethe multiple IP streams to a single IP stream corresponding to a singleservice.

The component splitter may divide (or separate) the data included in theIP stream, which is merged to a service and outputted by the streammerger, for each component, and may then output the data for eachcomponent to the buffer unit (220700). The component splitter may useaddress information, such as the IP address and the UDP port number, soas to switch to a buffer corresponding to each component included in thebuffer unit, thereby outputting the data corresponding to eachcomponent. The buffer unit (220700) may buffer the data corresponding toeach component in accordance with the output order of the IP stream.

Meanwhile, according to the embodiment of the present invention, atleast one of the components configuring a service may be divided into abase layer and an enhancement layer and then may be transmitted.

According to the embodiment of the present invention, by encoding videocomponent by using the SVC method, the component may be divided intobase layer data and enhancement layer data. The base layer datacorrespond to data for images having basic picture quality. Herein,although the base layer data are robust against the communicationenvironment, the picture quality of the base layer data is relativelylow. And, the enhancement layer data correspond to additional data forimages having higher picture quality. And, although the enhancementlayer data can provide high picture quality images, the enhancementlayer data are more or less resilient to the communication environment.

In the present invention, video data for terrestrial broadcasting may bedivided into base layer data and enhancement layer data. And, in orderto allow the video data for mobile broadcasting to flexibly respond tothe mobile broadcasting communication environment, the video data formobile broadcasting may be divided into base layer data and enhancementlayer data. The receiver may receive and decode only the base layervideo data, so as to acquire images having basic image quality. And, thereceiver may also receive and decode both the base layer video data andthe enhancement layer video data, so as to acquire images having ahigher picture quality. For example, the mobile receiver, such as amobile phone, a movable TV, and so on, may decode only the base layerdata, so as to provide images having basic picture quality, and afixed-type receiver, such as a general household TV, may decode both thebase layer data and the enhancement layer data, so as to provide imageshaving high picture quality.

At this point, the base layer data and the enhancement layer data may betransmitted through a single PLP, or may be transmitted throughdifferent PLPs.

FIG. 37 illustrates a block view showing the process of the broadcastingsignal receiver for receiving a PLP best fitting its purpose accordingto an embodiment of the present invention.

FIG. 37 shows an example of receiving a transmission frame, whichincludes a service configured of multiple PLPs, i.e., PLP1 to PLP4.

Herein, it will be assumed that PLP1 transmits SVC encoded base layerdata, that PLP2 transmits SVC encoded enhancement layer data, that PLP3transmits an audio stream, and that PLP4 transmits a data stream.

In the present invention, by adjusting and controlling the physicalparameters in accordance with the characteristics of the data includedin each PLP, the mobile reception performance or data communicationperformance may be differently set up, so that the receiver canselectively receive the required PLPs based upon the characteristics ofreceiver. Hereinafter, a detailed example will be described.

As shown in FIG. 37, since the PLP1 transmitting the base layer datashould be capable of being received by a general fixed-type receiver aswell as a mobile receiver, the broadcasting signal transmitting devicemay set up physical parameters for ensuring high reception performancerespective to PLP1 and may then transmit the set up parameters.

Additionally, the PLP2 transmitting the enhancement layer data have alower reception performance as compared to the PLP1. Accordingly, evenif the mobile receiver is incapable of receiving PLP2, in order to allowa fixed-type receiver, which is required to receive high picture qualitybroadcasting programs having high resolution, the broadcasting signaltransmitting device may set up and transmit physical parameters of PLP2.

Accordingly, as shown in FIG. 37, the mobile receiver may decode PLP1transmitting a video stream of the base layer, and may decode PLP3 andPLP4 transmitting audio and data streams, so as to provide a servicehaving general (or standard) resolution.

Alternatively, the fixed-type receiver may decode all of PLP1transmitting a video stream of the base layer, PLP2 transmitting a videostream of the enhancement layer, and PLP3 and PLP4 transmitting audioand data streams, so as to provide a service having high picturequality.

However, this is merely exemplary, and, therefore, the mobile receivermay also decode all of PLP1 transmitting a video stream of the baselayer, PLP2 transmitting a video stream of the enhancement layer, PLP3transmitting an audio stream, and PLP4 transmitting a data stream, so asto provide a service having high picture quality.

Meanwhile, according to an embodiment of the present invention, afterperforming SVC decoding on the video data, the broadcasting signaltransmitting device according to the present invention may transmit baselayer data by using a non-MIMO method, and the broadcasting signaltransmitting device may transmit enhancement layer data by using a MIMOmethod. In the present invention, a broadcasting signal transmittingsystem supporting the MIMO method will be referred to as a MIMOtransmitting system.

Hereinafter, diverse embodiments of the MIMO transmitting system usingSVC will be described in detail.

FIG. 38 illustrates a MIMO transmission system using an SVC and abroadcast signal transmitting method according to an embodiment of thepresent invention.

As shown in FIG. 38, the MIMO transmitting system may include an SVCencoder (244100), which encodes broadcasting data by using the SVCmethod, and a MIMO encoder (244200), which distributes data by using aspatial diversity or spatial multiplexing method, so that the data canbe transmitted to multiple antennae. Hereinafter, the MIMO encoder mayalso be referred to as a MIMO processor.

FIG. 38 shows an exemplary broadcast signal transmitting apparatus,which uses a Hierarchical modulation method.

The SVC encoder (244100) performs SVC encoding on the broadcast data andoutputs the SVC-encoded data as the base layer data and the enhancementlayer data. The base layer data are equally transmitted from a 1^(st)transmission antenna (Tx1; 244300) and a 2^(nd) transmission antenna(Tx2; 244400). And, the enhancement layer data are processed with MIMOencoding by the MIMO encoder (244200), thereby being respectivelyoutputted through the 1^(st) transmission antenna (244300) and the2^(nd) transmission antenna (244400) as identical data or as differentdata. In this case, the constellation mapper of the transmitting systemperform symbol mapping on the corresponding symbol in accordance withthe modulation type, as shown on the left-side drawing. For example, theconstellation mapper may perform layer modulation, so as to map bitscorresponding to the base layer to an MSB (Most Significant Bit) portionof the corresponding symbol, and to map bits corresponds to theenhancement layer to an LSB (Least Significant Bit) portion of thecorresponding symbol.

The receiving system may use a constellation demapper, so as to separatethe base layer data and the enhancement layer data from the demodulatedbit information and to acquire the separated data. The enhancement layerdata may be processed with MIMO decoding, so as to be acquired by usingbit information of a final SVC. In case the bit informationcorresponding to the MIMO cannot be separated, the receiver may use onlythe bit information corresponding to the SISO or the MISO, so as toacquire the base layer data and to provide the respective service.

FIG. 39 illustrates a MIMO transmission system using an SVC and abroadcast signal transmitting method according to another embodiment ofthe present invention.

As shown in FIG. 39, the MIMO transmitting system may include an SVCencoder (245100), which encodes broadcasting data by using the SVCmethod, and a MIMO encoder (245200), which distributes data by using aspatial diversity or spatial multiplexing method, so that the data canbe transmitted to multiple antennae. FIG. 39 illustrates an exemplarytransmitting system using a hybrid modulation method or an FDM(Frequency Division Multiplexing) method.

The SVC encoder (245100) performs SVC encoding on the broadcast data andoutputs the SVC-encoded data as the base layer data and the enhancementlayer data. The base layer data are equally transmitted from a 1^(st)transmission antenna (Tx1; 245300) and a 2^(nd) transmission antenna(Tx2; 245400). And, the enhancement layer data are processed with MIMOencoding by the MIMO encoder (245200), thereby being respectivelyoutputted through the 1^(st) transmission antenna (245300) and the2^(nd) transmission antenna (245400) as identical data or as differentdata.

At this point, in order to enhance data transmission efficiency, theMIMO transmitting system of FIG. 39 may process data by using the FDMmethod. Most particularly, by using the OFDM method, the MIMOtransmitting system may transmit data through multiple subcarriers. Asdescribed above, the transmitting system using the OFDM method mayallocate subcarriers as a subcarrier used for transmitting SISO/MISOsignals and as a subcarrier used for transmitting an MIMO signal,thereby being capable transmitting each signal. The base layer databeing outputted from the SVC encoder (245100) may be equally transmittedfrom multiple antennae through the SISO/MISO carrier, and theenhancement layer data being processed with MIMO encoding may betransmitted from multiple antennae through the MIMO carrier.

The receiving system receives an OFDM symbol. Then, the receiving systemperforms SISO/MISO decoding on the data corresponding to the SISO/MISOcarrier, so as to acquire the base layer data. And, the receiving systemperforms MIMO decoding on the data corresponding to the MIMO carrier, soas to acquire the enhancement layer data. Thereafter, based upon thechannel status and the receiving system, when the MIMO decoding processcannot be performed, the decoding process may be performed by using onlythe base layer data. Alternatively, when the MIMO decoding process canbe performed, the decoding process may be performed by using both thebase layer data and the enhancement layer data. Thus, a correspondingservice may be provided. In case of the second embodiment of the presentinvention, since the MIMO processing may be performed after mapping thebit information of the service to a symbol, the MIMO encoder (245200)may be positioned after the constellation mapper. Accordingly, thestructure of the receiving system may be more simplified as compared tothe structure of the receiving system shown in FIG. 38.

FIG. 40 illustrates a MIMO transmission system using an SVC and abroadcast signal transmitting method according to yet another embodimentof the present invention.

As shown in FIG. 40, the MIMO transmitting system may include an SVCencoder (246100), which encodes broadcasting data by using the SVCmethod, and a MIMO encoder (246200), which distributes data by using aspatial diversity or spatial multiplexing method, so that the data canbe transmitted to multiple antennae. FIG. 40 illustrates an exemplarytransmitting system using a layer PLP method or a TDM method.

In the embodiment shown in FIG. 40, the transmitting system mayrespectively transmit SVC-encoded base layer data and SVC-encodedenhancement layer data through an SISO/MISO slot and a MIMO slot. Thisslot may correspond to a time unit slot or a frequency unit slot of thetransmission signal. And, in the embodiment shown in FIG. 40, the slotis illustrated as a time unit slot. Furthermore, this slot may alsocorrespond to a PLP.

The receiving system may determine the slot type of the slot that isbeing received. And, the receiving system may receive base layer datafrom the SISO/MISO slot, and the receiving system may receiveenhancement layer data from the MIMO slot. And, as described above,based upon the channel and the receiving system, when the MIMO decodingprocess cannot be performed, the decoding process may be performed byusing only the base layer data. Alternatively, when the MIMO decodingprocess can be performed, the decoding process may be performed by usingboth the base layer data and the enhancement layer data. Thus, acorresponding service may be provided.

According to the embodiment of the present invention, the MIMO encoder(244200, 245200, 246200) of FIG. 38 to FIG. 40 may use at least one ofthe MIMO encoding methods proposed in the first embodiment to the thirdembodiment. This is merely exemplary, and, therefore, the MIMO encodingprocess may also be performed by using the SM method or the GC method.

In the present invention, the base layer data and the enhancement layerdata may be transmitted by using one PLP. And, each of the base layerdata and the enhancement layer data may be respectively transmitted byusing different PLPs.

According to an embodiment of the present invention, the base layer datamay be transmitted through a T2 frame (i.e., a terrestrial broadcastingframe), and the enhancement layer data may be transmitted through an FEFpart.

According to another embodiment of the present invention, the base layerdata and the enhancement layer data may only be transmitted through theFEF part.

In the description of the present invention, the FEF part, whichtransmits the base layer data and the enhancement layer data, will bereferred to as a MIMO broadcasting frame for simplicity. Herein, theMIMO broadcasting frame will be used in combination with a signal frameor a transmission frame.

Also, in the description of the present invention, the base layer dataand the enhancement layer data will be collectively referred to as MIMObroadcasting data for simplicity.

Hereinafter, in the following description of the present invention, theMIMO broadcasting data may be generated by any one of the 1^(st) methodto 3^(rd) method, which will be described as presented below, therebybeing transmitted. Alternatively, the MIMO broadcasting data may also begenerated and transmitted by a combination of at least one or more ofthe 1^(st) method to 3^(rd) method described below.

(1) Method for Transmitting MIMO Broadcasting Data to a Specific PLP

In the present invention, a method for including MIMO broadcasting datato a specific PLP and transmitting the specific PLP, afterdifferentiating the specific PLP from a PLP including the terrestrialbroadcasting (e.g., T2 broadcasting) data may be used. In this case, thespecific PLP may be used in order to transmit the MMO broadcasting data.And, at this point, additional information on the specific PLP may besignaled, so as to prevent any malfunction in the conventional receivingsystem from occurring. Hereinafter, the specific PLP including the MMObroadcasting data may be referred to as a MIMO broadcasting PLP, and thePLP including the terrestrial broadcasting data may be referred to as aterrestrial broadcasting PLP.

Since the conventional terrestrial broadcasting signal receivingapparatus may not be capable of processing the MIMO broadcasting data,additional information for identifying the terrestrial broadcasting PLPand the MIMO broadcasting PLP is required to be signaled. At this point,the signaling of the information for identifying the PLP type may use areserved field included in the L1 signaling information. For example, inorder to identify the PLP type, a PLP_TYPE field of theL1-post-signaling information may be used. At this point, the MIMObroadcasting PLP may be indicated by using any one of the values rangingfrom 011˜111 as the PLP_TYPE field value.

When transmitting the PLP, in order to acquire a more enhancedrobustness, a new modulation method and a new coding rate of the errorcorrection code may be used. In this case, in order to identify suchmodulation method and coding rate of the error correction code, theL1-post-signaling information may be used. According to an embodiment ofthe present invention, the present invention may use a PLP_COD field ofthe L1-post-signaling information in order to indicate the coding rateof the MIMO broadcasting PLP. For example, in order to identify thecoding rate of the MIMO broadcasting PLP, any one of 110 or 111 may beused as the PLP_COD field value.

Furthermore, according to an embodiment of the present invention, thepresent invention may use a PLP_MOD field of the L1-post-signalinginformation in order to indicate a modulation method of the MIMObroadcasting PLP. For example, in order to identify the modulationmethod of the MIMO broadcasting PLP, any one of values 100 to 111 may beused as the PLP_MOD field value.

At this point, the base layer data and the enhancement layer dataconfiguring the MIMO broadcasting data may be collectively transmittedto a single PLP, or may be separately transmitted to each PLP. Forexample, when the base layer data are transmitted to the PLP of the baselayer, and when the enhancement layer data are transmitted to the PLP ofthe enhancement layer, the receiving apparatus may use a PLP_PROFILEfield, so as to indicate whether the current PLP corresponds to the baselayer PLP or to the enhancement layer PLP.

(2) Method for Transmitting MIMO Broadcasting Data to a Specific Frames

In the present invention, a method for including MIMO broadcasting datato a specific frame and transmitting the specific frame, afterdifferentiating the specific frame from a frame including theconventional terrestrial broadcasting data may be used. In this case,the specific frame may be used in order to transmit the MMO broadcastingdata. And, at this point, additional information on the specific framemay be signaled, so as to prevent any malfunction in the conventionalreceiving system from occurring. Hereinafter, the specific frameincluding the MMO broadcasting data may be referred to as a MIMObroadcasting frame, and the frame including the terrestrial broadcastingdata may be referred to as a terrestrial broadcasting frame.Additionally, in case the specific frame including the MIMO broadcastingframe corresponds to an FEF, the FEF may be referred to as an MIMObroadcasting frame.

The present invention may differentiate the terrestrial broadcastingdata from the MIMO broadcasting data in frame units and may transmit thedifferentiated data accordingly. And, at this point, by identifying aframe by using the L1 signaling information, and by ignoring (ordisregarding) the MIMO broadcasting frame, the convention terrestrialbroadcasting receiving apparatus may be prevented from malfunctioning.

(3) Method for Transmitting a MIMO Broadcasting PLP to a TerrestrialBroadcasting Frame and a MIMO Broadcasting Frame

The present invention may transmit a PLP including the MIMO broadcastingdata through a terrestrial broadcasting frame and a MIMO broadcastingframe. For example, the base layer data may be transmitted through theterrestrial broadcasting frame, and the enhancement layer data may betransmitted through the MIMO broadcasting frame. In this case, unlikethe above-described embodiments of the present invention, since a MIMObroadcasting PLP also exists in the terrestrial broadcasting frame, arelation between interconnected PLPs existing in the terrestrialbroadcasting frame and in the MIMO broadcasting frame, is required to besignaled. In order to do so, the L1 signaling information should also beincluded in the MIMO broadcasting frame, and the information on the MIMObroadcasting PLP, which exists within the frame, may be transmittedalong with the L1 signaling information of the terrestrial broadcastingframe.

Fields respective to the PLP being included in the L1-post-signalinginformation of each frame may be used for the connection between theMIMO broadcasting PLPs existing in different frames. For example, thereceiving system may use at least one of a PLP_ID field, a PLP_TYPEfield, a PLP_PAYLOAD_TYPE field, and a PLP_GROUP_ID field, which areincluded in the L1-post-signaling information, so as to verify theinterconnection relation of the MIMO broadcasting PLPs included indifferent frames. Then, desired MIMO broadcasting PLPs may beconsecutively decoded, so as to acquire a service.

The terrestrial broadcasting PLP existing in the conventionalterrestrial broadcasting frame (i.e., T2 frame) may be pre-defined bythe terrestrial broadcasting system, so as to be transmitted to asupported transmission mode. Also, as described above, the terrestrialbroadcasting PLP may be transmitted in a new transmission modesupporting the MIMO system. For example, as described above, a MIMObroadcasting PLP being included in the terrestrial broadcasting framemay be transmitted in a transmission mode of terrestrial broadcasting asa base layer by using the MISO or SISO method, and a MIMO broadcastingPLP being included in the MIMO broadcasting frame may be transmitted asan enhancement layer by using the MIMO method.

FIG. 41(a) illustrates an exemplary super frame structure according toanother embodiment of the present invention. Herein, FIG. 41(a) shows anexample of transmitting a base layer PLP through a terrestrialbroadcasting frame and transmitting an enhancement layer PLP through aMIMO broadcasting frame (i.e., FEF part). At this point, a PLP includingbase layer data may be transmitted by using an SISO method or a MISOmethod. And, a PLP including enhancement layer data may be transmittedby using an SISO method, a MISO method, or a MIMO method.

FIG. 41(b) illustrates an exemplary super frame structure according toyet another embodiment of the present invention. Herein, FIG. 41(b)shows an example of transmitting both a base layer PLP and anenhancement layer PLP through a MIMO broadcasting frame (i.e., FEFpart).

At this point, a base layer PLP including base layer data may betransmitted by using an SISO method or a MISO method. And, anenhancement layer PLP including enhancement layer data may betransmitted by using an SISO method, a MISO method, or a MIMO method. Asdescribed above, the ratio between the base layer PLP and theenhancement layer PLP within the MIMO broadcasting frame may vary withina range of 0˜100%.

FIG. 41(c) illustrates an exemplary super frame structure according toyet another embodiment of the present invention. Herein, FIG. 41(c)shows an example of transmitting both base layer data and enhancementlayer data through a MIMO broadcasting frame (i.e., FEF part). However,unlike in the example shown in FIG. 41(b), in the example shown in FIG.41(c), the base layer and the enhancement layer are transmitted by beingdifferentiated as carriers, instead of being differentiated as PLPs.More specifically, the data corresponding to the base layer and the datacorresponding to the enhancement layer may respectively be allocated toeach separate subcarrier, so as to be processed with OFDM modulation,thereby being transmitted.

FIG. 42 illustrates a broadcasting signal transmitting device accordingto another embodiment of the present invention.

The broadcasting signal transmitting device of FIG. 42 corresponds to anexemplary embodiment, which identifies the base layer data as the baselayer PLP, and which the enhancement layer data as the enhancement layerPLP, thereby transmitting the identified (or differentiated) PLPs.Although it is not shown in FIG. 42, the broadcasting signaltransmitting device includes an SVC encoder, which performs SVC encodingon data, so as to transmit the SVC encoded data as base layer data andenhancement layer data. At this point, according to the embodiment ofthe present invention, it is described herein that the base layer dataare included in PLP1, and that the enhancement layer data are includedin PLP2.

The broadcasting signal transmitting device of FIG. 42 includes a firstBICM module (258100) for performing BICM processing on a base layer PLP(PLP1), a second BICM module (258200) for performing BICM processing onan enhancement layer PLP (PLP2), a frame builder (258300) receiving PLPsthat are processed in the first and second BICM modules (258200),thereby building a frame, a MIMO encoder (258400) performing MIMO, MISO,or SISO processing on the output data of the frame builder (258300), afirst OFDM generator (258500) performing OFDM modulation on a firsttransmission signal, which is outputted from the MIMO encoder (258400),and a second OFDM generator (258600) performing OFDM modulation on asecond transmission signal, which is outputted from the MIMO encoder(258400).

Reference may be made on the description of the operations of the blocksincluded in the above-described broadcasting signal transmitting devicehaving the same names as the first BICM module (258100), the second BICMmodule (258200), the frame builder (258300), the MIMO encoder (258400),the first OFDM generator (258500), and the second OFDM generator(258600), and, therefore, a detailed description of the same will beomitted herein.

In the broadcasting signal transmitting device of FIG. 42, the MIMOencoder (258400) may be positioned between a constellation mapper and atime interleaver within the second BICM module (258200).

FIG. 43 illustrates a broadcasting signal receiving device according toyet another embodiment of the present invention.

When the base layer and the enhancement layer are identified andtransmitted as PLPs, as shown in FIG. 42, the broadcasting signalreceiving device of FIG. 43 corresponds to an exemplary embodiment of abroadcasting signal receiving device receiving and processing such PLPs.Although it is not shown in FIG. 43, the broadcasting signal receivingdevice includes an SVC decoder, which performs SVC decoding on baselayer and enhancement data, so as to recover the data. At this point,according to the embodiment of the present invention, the base layerdata are included in PLP1, and the enhancement layer data are includedin PLP2, thereby being received.

The broadcasting signal receiving device of FIG. 43 includes OFDMdemodulators (259100, 259200) performing OFDM demodulation on signalsreceived through multiple antennae, an MIMO decoder (259300) performingMIMO decoding on the signals OFDM-demodulated from the OFDM demodulators(259100, 259200) in accordance with the channel characteristics, a framedemapper (259400) outputting base layer PLP and enhancement layer PLPfrom the signal frame including the MIMO-decoded signal, and BICMdecoder (259500, 259600) each performing an inverse process of the BICMmodule for each PLP and correcting errors occurring due to thetransmission channel.

For the detailed description on the operations of each of the OFDMdemodulators (259100, 259200), the MIMO decoder (259300), the framedemapper (259400), and the BICM decoders (259500, 259600) of thebroadcasting signal receiving device shown in FIG. 43, reference may bemade to the description on the operations of the same blocks included inthe above-described broadcasting signal receiving device. And,therefore, detailed description of the same will be omitted.

The broadcasting signal receiving device of FIG. 43 may first acquirebase layer data from the PLP (PLP1), which is outputted from the firstBICM decoder (259500), and enhancement layer data from the PLP (PLP2),which is outputted from the second BICM decoder (259600), and may thenperform SVC decoding on the acquired data, so as to provide a respectiveservice. In case the broadcasting signal receiving device acquires onlythe base layer data, the broadcasting signal receiving device may decodethe base layer data, so as to provide a basic service. And, in case thebroadcasting signal receiving device acquires the base layer data alongwith the enhancement layer data, the broadcasting signal receivingdevice may provide a service having higher picture quality/soundquality.

Meanwhile, according to the embodiment of the present invention, in caseboth the base layer data and the enhancement layer data are transmittedby using a single PLP, a mux may be further included in from of the BICMmodule of the broadcasting signal receiving device shown in FIG. 42.

More specifically, the base layer data and the enhancement layer databeing outputted from the SVC encoder may be included in a single PLP(PLP1), so as to be inputted to the mux. In this case, the mux mayidentify the base layer data and the enhancement layer data, which areincluded in the PLP (PLP1), thereby outputting the identified data tothe respective BICM module (258100, 258200). In this case, thebroadcasting signal receiving device may be equipped with a timeinterleaver, and the base layer and the enhancement layer may be coupled(or combined) by the time interleaver, thereby being processed withinterleaving while the two layers are intermixed with one another. Thus,diversity of the time domain may be gained. At this point, according tothe embodiment of the present invention, the data corresponding to thebase layer within the PLP may be SISO or MIMO-processed, and the datacorresponding to the enhancement layer may be MIMO-processed.

Additionally, in case both the base layer data and the enhancement layerdata are both transmitted from the transmitting end by using a singlePLP, the frame demapper of the broadcasting signal receiving deviceshown in FIG. 43 extracts a PLP (PLP1), which includes the data of thebase layer and the data of the enhancement layer, and outputs theextracted PLP. In this case, the broadcasting signal receiving devicemay be equipped with a time deinterleaver, and the time deinterleavermay perform time deinterleaving on the PLP (PLP2), so as to divide thePLP into base layer data and enhancement layer data and to repositioneach data type within the time domain, thereby outputting therepositioned data type to each stream. Each of the BICM decoders(259500, 259600) processes a base layer stream and an enhancement layerstream.

At this point, the base layer data and the enhancement layer data, whichare error-corrected and outputted from the BICM decoders (259500,259600), may be SVC-decoded, so as to provide a service. In the casewhen only the base layer data are acquired, the base layer data may bedecoded, so as to provide the basic (or essential) service. And, whenboth the base layer data and the enhancement layer data are acquired, aservice having higher picture quality/sound quality may be provided.

In the broadcasting signal receiving device of FIG. 43, the MIMO decoder(259300) may also be located between the frame demapper (259400) and theBICM decoders (259500, 259600).

Hereinafter, a signaling method of the signaling method according to thepresent invention will be described in detail. The signal frameaccording to the present invention may be divided into a preamble regionand a data region, and the preamble region may be configured of a P1symbol and one or more P2 symbols, and the data region may be configuredof multiple data symbols. At this point, the preamble region may furtherinclude an AP1 symbol after the P1 symbol. And, in this case, the P1symbol and the AP1 symbol may be consecutively transmitted.

Herein, the P1 symbol transmits P1 signaling information, the AP1 symboltransmits AP1 signaling information, and the one or more P2 symbol eachtransmits L1 signaling information and signaling information included inthe common PLP (i.e., L2 signaling information). The signalinginformation being included in the common PLP may be transmitted througha data symbol. Therefore, in light of a signal frame over a physicallayer, the preamble region may include a P1 signaling information regionto which the P1 signaling information is signaled, an L1 signalinginformation region to which the L1 signaling information is signaled,and an entire portion or a partial portion of a common PLP region towhich the L2 signaling information is signaled. Herein, the common PLPregion may also be referred to as an L2 signaling information region. Ifa signal frame includes an AP1 symbol, the preamble region includes theP1 signaling information region, the AP1 signaling information region,the L1 signaling information region, and an entire portion or a partialportion of the common PLP region.

The L1 signaling information includes L1-pre-signaling information andL1-post-signaling information. The L1-post-signaling information thenincludes Configurable L1-post-signaling information, DynamicL1-post-signaling information, Extension L1-post-signaling information,and CRC information, and may further include L1 padding data.

FIG. 44 illustrates an exemplary syntax structure of P1 signalinginformation according to an embodiment of the present invention.

According to the embodiment of the present invention, in FIG. 44, the P1signaling information is assigned with 7 bits and includes a 3-bit S1field and a 4-bit S2 field. In the S2 field, among the 4 bits, the first3 bits are described as S2 field1 and the 1 bit is described as S2field2.

The S1 field signals a preamble format. For example, when the S1 fieldvalue is equal to 000, this indicates that the preamble corresponds to aT2 preamble, and that data are transmitted in an SISO format (T2_SISO).When the S1 field value is equal to 001, this indicates that thepreamble corresponds to a T2 preamble, and that data are transmitted inan MISO format (T2_MISO). When the S1 field value is equal to 010, thisindicates that the preamble corresponds to a non-T2 preamble.

The S2 field signals FFT size information. According to the embodimentof the present invention, the FFT size may correspond to 1 k, 2 k, 4 k,8 k, 16 k, and the GI size may correspond to 1/128, 1/32, 1/16, 19/256,⅛, 19/128, ¼. The FFT size signifies a number of subcarriers configuringa single OFDM symbol. When the S2 filed2 value is equal to 0, thisindicates that, in the current transmission, all preambles are beingtransmitted as the same type, and when the field value is equal to 1,this indicates that the preambles are each transmitted as differenttypes.

FIG. 45 illustrates an exemplary syntax structure of AP1 signalinginformation according to an embodiment of the present invention.

According to the embodiment of the present invention, in FIG. 45, theAP1 signaling information is assigned with 7 bits and includes a 4-bitPILOT_PATTERN field and a 3-bit L1 PRE_SPREAD_LENGTH field.

The PILOT_PATTERN field indicates a pilot pattern of the correspondingsignal frame. In the present invention, by transmitting pilot patterninformation through the AP1 symbol, even when the P2 symbol is nottransmitted, and even when the L1 signaling information is spread todata symbols of the data region, the receiver may be aware of the pilotpattern prior to decoding the L1 signaling information of the dataregion.

The L1_PRE_SPREAD_LENGTH field indicates a length of a section withinthe data region in which the L1-pre-signaling information is spread.More specifically, among the data symbols of the signal frame, thisfield indicates a number of data symbols included in a section to whichthe L1-pre-signaling information is being spread. In the presentinvention, the section to which the L1-pre-signaling information isbeing spread will be referred to as an L1 pre spread section. If theL1_PRE_SPREAD_LENGTH field value is equal to ‘000’, this indicates thatthe L1 signaling information is not spread in the data region of thecorresponding signal frame.

In FIG. 45, since the fields included in the AP1 signaling informationand significance of the values of each field are merely examples givento facilitate the understanding of the present invention, and since thefields that can be included in the AP1 signaling information and thesignificance of the respective field values may be easily modified byanyone skilled in the art, the present invention will not be limitedonly to the examples given herein.

FIG. 46 illustrates an exemplary syntax structure of L1-pre-signalinginformation according to an embodiment of the present invention. TheL1-pre-signaling information includes information required for decodingthe L1-post-signaling information.

The fields being included in the L1-pre-signaling information of FIG. 46will hereinafter be described in detail.

A TYPE field may be assigned with 8 bits and may indicate the type of aninput stream being transmitted in a super frame. More specifically, theinput stream may correspond to TS, GS, TS+GS, IP, and so on, and suchidentification may use the TYPE field.

A BWT_EXT field is assigned with 1 bit and may indicate whether or not abandwidth extension of an OFDM symbol is to be performed.

An S1 field is assigned with 3 bits and performs the same role as the S1field included in the P1 signaling information of FIG. 44. An S2 fieldis assigned with 4 bits and performs the same role as the S2 fieldincluded in the P1 signaling information of FIG. 44. According to theembodiment of the present invention, an L1_REPETITION_FLAG field isassigned with 1 bit and may indicate whether or not L1-post-signalinginformation related to the current frame is signaled to the P2 symbol.If the L1 signaling information of the next signal frame is configuredto have a structure to which the data symbols of the current signalframe are spread, the L1_REPETITION_FLAG field may also be used in orderto indicate whether or not the L1 signaling information of the nextsignal frame has been spread to the current signal frame. For example,when the L1_REPETITION_FLAG field is equal to 1, this indicates that theL1 signaling information has been spread to the current signal frame,and when the corresponding field is equal to 0, this indicates that theL1 signaling information has not been spread to the current signalframe.

A GUARD_INTERVAL field is assigned with 3 bits and indicates a GI sizeof the current transmission frame. The GI size indicates an occupationratio of the GI within a single OFDM symbol. Accordingly, the OFDMsymbol length may vary depending upon the FFT size and the GI size.

A PAPR field is assigned with 4 bits and indicates a PAPR reductionmethod. The PAPR method used in the present invention may correspond toan ACE method or a TR method.

An L1_MOD field is assigned with 4 bits and may indicate a QAMmodulation type of the L1-post-signaling information.

An L1_COD field is assigned with 2 bits and may indicate a code rate ofthe L1-post-signaling information.

An L1_FEC_TYPE field is assigned with 2 bits and may indicate an FECtype of the L1-post-signaling information.

An L1_POST_SIZE field is assigned with 18 bits and may indicate the sizeof the coded and modulated L1-post-signaling information.

An L1_POST_INFO_SIZE field is assigned with 18 bits and may indicate thesize of the L1-post-signaling information in bit units.

A PILOT_PATTERN field is assigned with 4 bits and may indicate adistributed pilot pattern that is inserted in the current signal frame.

A TX_ID_AVAILABILITY field is assigned with 8 bits and may indicate atransmitting device identification capability within the currentgeographical cell range.

A CELL_ID field is assigned with 16 bits and may indicate an identifieridentifying a geographical cell within a network for mobile broadcasting(NGH).

A NETWORK_ID field is assigned with 16 bits and may indicate anidentifier identifying the current network.

A SYSTEM_ID field is assigned with 16 bits and may indicate anidentifier identifying the system.

A NUM_NGH_FRAMES field is assigned with 8 bits and may indicate a numberof NGH frame within the current super frame.

A NUM_T2_FRAMES field is assigned with 8 bits and may indicate a numberof T2 frame within the current super frame. This field is useful fordetermining the super frame structure and may be used for calculatingthe information for directly hopping to the next NGH frame.

A L1_POST_SPREAD_LENGTH field is assigned with 12 bits and may indicatethe length of a section within the data region to which theL1-post-signaling information is being spread. More specifically, amongthe data symbols of the signal frame, this field may indicate the numberof data symbols being included in the section to which theL1-post-signaling information is being spread. In the present invention,the section to which the L1-post-signaling information is being spreadwill be referred to as an L1 post spread section. If all of theL1_POST_SPREAD_LENGTH field value is equal to 0, this signifies that theL1-post-signaling information is not spread to the data region of thecorresponding signal frame.

A NUM_DATA_SYMBOLS field is assigned with 12 bits and may indicate anumber of data symbols included in the current signal frame, with theexception for the P1, AP1, P2 symbols.

A NUM_MISO_SYMBOLS field is assigned with 12 bits and may indicate anumber of MISO symbols among the diverse data symbols.

A MIMO_SYMBOL_INTERVAL field is assigned with 12 bits and may indicate anumber of MISO symbols between two MIMO symbol parts.

A MIMO_SYMBOL_LENGTH field is assigned with 12 bits and may indicate anumber of MIMO symbols in one MIMO symbol part.

A REGEN_FLAG field is assigned with 3 bits and may indicate and mayindicate a number of signal regeneration performed by the repeater.

An L1_POST_EXTENSION field is assigned with 1 bit and may indicatewhether or not an extension field exits in the L1-post-signalinginformation.

A NUM_RF field is assigned with 3 bits and may indicate a number of RFswithin the current system.

A CURRENT_RF_IDX field is assigned with 3 bits and may indicate an indexof the current RF channel.

A RESERVED field is assigned with 10 bits and corresponds to a fieldthat is reserved for future usage.

A CRC-32 field is assigned with 32 bits and may indicate a CRC errorextraction code of the 32 bits.

In FIG. 46, since the fields included in the L1-pre-signalinginformation and significance of the values of each field are merelyexamples given to facilitate the understanding of the present invention,and since the fields that can be included in the L1-pre-signalinginformation and the significance of the respective field values may beeasily modified by anyone skilled in the art, the present invention willnot be limited only to the examples given herein.

FIG. 47 illustrates an exemplary syntax structure of configurableL1-post-signaling information according to an embodiment of the presentinvention. The configurable L1-post-signaling information may includeparameters required by the receiver for decoding a PLP and, moreparticularly, configurable L1-post-signaling information may includediverse information that can be equally applied during a signal frame.

The fields being included in the configurable L1-post-signalinginformation of FIG. 47 will hereinafter be described in detail.

A SUB_SLICES_PER_FRAME field is assigned with 15 bits and may indicate anumber of sub-slices included in a signal frame.

A NUM_PLP field is assigned with 8 bits and may indicate a number ofPLPs within the current super frame.

A NUM_AUX field is assigned with 4 bits and may indicate a number ofauxiliary streams.

An AUX_CONFIG_RFU field is assigned with 8 bits and corresponds to aregion reserved for a future usage.

Subsequently, a for loop (hereinafter referred to as a frequency loop),which is repeated as many times as the number of RFs within the currentsystem, is signaled. The NUM_RF field is signaled to theL1-pre-signaling information.

Hereinafter, fields being included in the frequency loop will bedescribed in detail.

An RF_IDX field is assigned with 3 bits and may indicate an index ofeach frequency within an RF channel.

A FREQUENCY field is assigned with 32 bits and may indicate a centerfrequency of the RF channel.

An FEF_TYPE field, an FEF_LENGTH field, and an FEF_INTERVAL field, whichare shown below, correspond to fields that are used only when the LSB ofthe S2 field is equal to 1, i.e., when the S2 field is expressed asS2=‘xxx1’.

The FEF_TYPE field is assigned with 4 bits and may indicate an FEF(Future extension frame) type.

The FEF_LENGTH field is assigned with 22 bits and may indicate a numberof elementary periods of a related FEF part.

The FEF_INTERVAL field is assigned with 8 bits and may indicate a numberof T2 frames existing between two FRF parts.

A NEXT_NGH_SUPERFRAME field is assigned with 8 bits and may indicate anumber of super frames existing between the current super frame and thenext super frame, which includes the next NGH frame.

A RESERVED_2 field is assigned with 32 bits and corresponds to a fieldthat is reserved for a future usage.

Subsequently, a for loop (hereinafter referred to as an auxiliary streamloop), which is repeated as many times as the number of auxiliarystreams (NUM_AUX field value-1), is signaled, a 32-bit AUX_RFU field,which is reserved for a future usage, is included herein.

Subsequently, a for loop (hereinafter referred to as a PLP loop), whichis repeated as many times as the number of PLPs within the current superframe (NUM_PLP field value-1), is signaled.

Hereinafter, fields being included in the PLP loop will be described indetail.

A PLP_ID field is assigned with 8 bits and may indicate an identifieridentifying the corresponding PLP.

A PLP_TYPE field is assigned with 3 bits and may indicate whether thecorresponding PLP corresponds to a common PLP, a Type1 data PLP, or aType2 data PLP. Additionally, the PLP_TYPE field may indicate whetherthe corresponding PLP corresponds to a PLP being included in a pluralityof PLP groups, or to a group PLP being included in a single PLP group.

A PLP_PAYLOAD_TYPE field is assigned with 5 bits and may indicate thetype of a PLP payload. More specifically, the data included in thepayload of the PLP may correspond to GFPS, GCS, GSE, TS, IP, and so on,and such identification may use the PLP_PAYLOAD_TYPE field.

The PLP_PROFILE field is assigned with 2 bits and may indicate a profileof the corresponding PLP. More specifically, this field indicateswhether the corresponding field is a mandatory (or required) PLP or anoptional (or selective) PLP. For example, when the PLP of the video datais identified as a PLP for transmitting a base layer and a PLP fortransmitting an enhancement layer, the PLP transmitting the base layerbecomes the mandatory PLP, and the PLP transmitting the enhancementlayer becomes the optional PLP. Additionally, the common PLP correspondsto a mandatory PLP. More specifically, depending upon the receivercharacteristic, such as a mobile receiver, a fixed-type receiver, and soon, the receiver may use the PLP_PROFILE[PLP_PROFILE] field so as toverify by which receiver the component of the broadcast service beingtransmitted to the current PLP may be used, and depending upon thereceiver characteristic, the receiver may determine whether or not toreceive the current PLP.

An FF_FLAG field is assigned with 1 bit and, when 2 or more RF channelsare being used, this field may indicate a fixed frequency mode.

A FIRST_RF_IDX field is assigned with 3 bits and may indicate an RFindex of a first signal frame of the corresponding PLP.

A FIRST_FRAME_IDX field is assigned with 8 bits and may indicate a frameindex of the first signal frame of the corresponding PLP.

A PLP_GROUP_ID field is assigned with 8 bits and may indicate anidentifier identifying a PLP group related to the corresponding PLP.

A PLP_COD field is assigned with 3 bits and may indicate the code rateof the corresponding PLP. In the present invention, any one of the coderates of 1/4, 1/3, 2/5, 1/2, 3/5, 2/3, 3/4, 4/5, 5/6 may be used in thecorresponding PLP.

A PLP_MOD field is assigned with 3 bits and may indicate a constellationsize (i.e., modulation format) of the corresponding PLP. In the presentinvention, any one of the modulation formats (or modulations types) ofBPSK, QPSK, 16QAM, 64QAM, 256QAM may be used.

A PLP_MIMO_TYPE field is assigned with 2 bits and may indicate whetherthe corresponding PLP corresponds to a MIMO type or a MISO type.

For example, a PLP_MOD field value, i.e., the constellation size may bedecided by a combination with the PLP_MIMO_TYPE field. If thePLP_MIMO_TYPE field value indicates the MISO, the PLP_MOD field may beused for symbol re-mapping. If the PLP_MIMO_TYPE field value indicatesthe MIMO, after performing MIMO processing, the PLP_MOD field may beinterpreted as a constellation size having a spectrum effect, as aresult of the MIMO processing.

A PLP_ROTATION field is assigned with 1 bit and may indicate whether ornot constellation rotation and re-mapping of the PLP has been used.

A PLP_FEC_TYPE field is assigned with 2 bits and may indicate an FECtype of the corresponding PLP.

A PLP_NUM_BLOCKS_MAX field is assigned with 10 bits and may indicate amaximum number of PLPs included in the FEC blocks.

A FRAME_INTERVAL field is assigned with 8 bits and may indicate a T2frame interval within a super frame, when inter-frame interleaving isapplied.

A TIME_IL_LENGTH field is assigned with 8 bits and may indicate a timeinterleaver length (or depth).

A TIME_IL_TYPE field is assigned with 1 bit and may indicate the timeinterleaver type.

An IN_BAND_FLAG field is assigned with 1 bit and may indicate whether ornot in-band signaling exists.

A RESERVED_1 field is assigned with 16 bits and corresponds to a fieldthat is reserved in the PLP loop for a future usage.

The PLP loop may further include a PLP_COMPONENT_TYPE field. ThePLP_COMPONENT_TYPE field is assigned with 8 bits and may indicate thetype of data (or service component) being transmitted through thecorresponding PLP. Therefore, based upon the PLP_COMPONENT_TYPE field,the receiver may be capable of determining whether the type of thecomponent being transmitted through the corresponding PLP corresponds tobase layer video component, an enhancement layer video component, anaudio component, or a data component.

According to an embodiment of the present invention, the PLP group mayalso be referred to as an LLP (Link-Layer-Pipe), and the PLP_GROUP_IDfield may also be referred to as an LLP_ID field. Most particularly, anNIT, which is to be described later on, includes a PLP_GROUP_ID field,which is identical to the PLP_GROUP_ID field included in the L1signaling information. And, the NIT may also include atransport_stream_id field for identifying a transmission stream relatedto the PLP group. Therefore, by using the NIT, the receiver may becapable of knowing to which PLP group a specific stream is related. Morespecifically, in order to simultaneously decode streams (e.g., TSs)being transmitted through PLPs having the same PLP_GROUP_ID, the streamsthat are indicated by the transport_stream_id field of the NIT may bemerged, thereby being capable of recovering a single service stream.

Therefore, when the broadcasting signal is being transmitted in a TSformat, the receiver may merge the PLPs having the same PLP_GROUP_IDfield, so as to recover the initial (or original) TS.

If the broadcasting signal is transmitted in an IP format, the receivermay use the PLP_GROUP_ID field, so as to locate and find the servicecomponents related to a single service. And, by merging such servicecomponents, a single service may be recovered. Accordingly, the receivershould be capable of simultaneously receiving PLPs having the samePLP_GROUP_ID.

In FIG. 47, since the fields included in the configurableL1-post-signaling information and significance of the values of eachfield are merely examples given to facilitate the understanding of thepresent invention, and since the fields that can be included in theconfigurable L1-post-signaling information and the significance of therespective field values may be easily modified by anyone skilled in theart, the present invention will not be limited only to the examplesgiven herein.

FIG. 48 illustrates an exemplary syntax structure of dynamicL1-post-signaling information according to an embodiment of the presentinvention. The dynamic L1-post-signaling information may includeparameters required by the receiver for decoding a PLP and, moreparticularly, the dynamic L1-post-signaling information may includecharacteristic information corresponding to a signal frame that iscurrently being transmitted. Additionally, the dynamic L1-post-signalinginformation may also be signaled to an in-band, so that that thereceiver can efficiently process slicing.

The fields being included in the dynamic L1-post-signaling informationof FIG. 48 will hereinafter be described in detail.

A FRAME_IDX field is assigned with 8 bits and may indicate an index of acurrent signal frame within the super frame. For example, an index ofthe first signal frame within the super frame may be set to 0.

A SUB_SLICE_INTERVAL field is assigned with 22 bits and may indicate anumber of OFDM cell existing between two sub-slices within the same PLP.

A TYPE_2_START field is assigned with 22 bits and may indicate astarting position among the OFDM cells of the Type2 data PLPs.

An L1_CHANGE_COUNTER field is assigned with 8 bits and may indicate anumber of super frame that remain before the L1 configuration (e.g.,contents of the fields included in the L1 pre signaling or content of aconfigurable part in the L1 post signaling).

A START_RF_IDX field is assigned with 3 bits and may indicate a start RFindex of a next signal frame.

A RESERVED_1 field is assigned with 8 bits and corresponds to a fieldthat is reserved for a future usage.

A NEXT_NGH_FRAME field is assigned with 8 bits and corresponds to afield that is used only when the LSB of the S2 field is equal to 1,i.e., when the S2 field is expressed as S2=‘xxx1’. A NEXT_NGH_SUPERFRAMEfield indicates a number of T2 or FEF frames existing between the firstT2 frame within the next super frame, which includes an NGH frame, andthe next NGH frame. The NEXT_NGH_FRAME field and the NEXT_NGH_SUPERFRAMEfield may be used by the receiver for calculating a hopping amount forhopping to the next NGH frame. More specifically, the NEXT_NGH_FRAMEfield and the NEXT_NGH_SUPERFRAME field provide an efficient hoppingmechanism, when a large number of T2 frames are mixed with the FEF, andwhen not all of the FEFs are used only for the NGH frames. Mostparticularly, the receiver may perform hopping to the next NGH framewithout having to detect the P1 signaling information of all signalframes existing in the super frame and to decode the detected P1signaling information.

Subsequently, a for loop (hereinafter referred to as a PLP loop), whichis repeated as many times as the number of PLPs existing within thecurrent super frame (NUM_PLP field value-1), is signaled.

A PLP_ID field, a PLP_START field, and a PLP_NUM_BLOCKS field areincluded in the PLP loop. And, the corresponding field will hereinafterbe described in detail.

The PLP_ID field is assigned with 8 bits and may indicate an identifieridentifying a PLP.

The PLP_START field is assigned with 22 bits and may indicate a startingposition of OFDM cells of the current PLP.

The PLP_NUM_BLOCKS field is assigned with 10 bits and may indicate anumber of FEC blocks related to the current PLP.

A RESERVED_2 field is assigned with 8 bits and corresponds to a fieldincluded in the PLP loop that is reserved for a future usage.

A RESERVED_3 field is assigned with 8 bits and corresponds to a fieldthat is reserved for a future usage.

Field included in an auxiliary stream loop will hereinafter bedescribed.

Subsequently, a for loop (hereinafter referred to as an auxiliary streamloop), which is repeated as many times as the number of auxiliarystreams (NUM_AUX field value-1), is signaled, and a 48-bit AUX_RFU fieldis included herein for a future usage.

In FIG. 48, since the fields included in the dynamic L1-post-signalinginformation and significance of the values of each field are merelyexamples given to facilitate the understanding of the present invention,and since the fields that can be included in the dynamicL1-post-signaling information and the significance of the respectivefield values may be easily modified by anyone skilled in the art, thepresent invention will not be limited only to the examples given herein.

Meanwhile, the present invention may signal a PLP or a correlationbetween a PLP and service components, by using at least one of thePLP_GROUP_ID field, the PLP_TYPE field, the PLP_PROFILE field, and thePLP_COMPONENT_TYPE field of the PLP loop within the configurableL1-post-signaling information. Additionally, the present invention mayalso know the operation characteristics, such as the mobile performanceand data communication characteristics, of the PLP by using the PLP_CODfield and the PLP_MOD field.

Hereinafter, a signaling method for signaling a PLP or a correlationbetween a PLP and service components, by using the PLP_ID field, thePLP_GROUP_ID field, the PLP_COMPONENT_TYPE field, and the PLP_PROFILEfield, will be described in detail.

Hereinafter, the present invention provides a signaling method accordingto 4 different exemplary embodiments of the present invention. The 4different exemplary embodiments may be divided into cases when thebroadcast signal is being transmitted in a TS format and cases when thebroadcast signal is being transmitted in an IP format. In thedescription of the present invention, the first exemplary embodiment tothe third exemplary embodiment correspond to a signaling method whereinthe broadcast signal is transmitted in the TS format, and the fourthexemplary embodiment corresponding to a signaling method wherein thebroadcast signal is transmitted in the IP format.

Each exemplary embodiment of the present invention will be described indetail as presented below.

The first embodiment of the present invention corresponds to a signalingmethod enabling the receiver to merge PLPs included in the same PLPgroup by using the correlation between the PLP group, which is includedin the L1 signaling information region, and a service, thereby enablingthe receiver to recover a transport stream.

Just as in the first embodiment of the present invention, in addition toenabling the receiver to merge PLPs included in the same PLP group byusing the correlation between the PLP group, which is included in the L1signaling information region, and a service, thereby enabling thereceiver to recover a transport stream, the second embodiment of thepresent invention corresponds to a signaling method also enabling thereceiver to selectively receive desired PLPs in accordance with thereceiver characteristic, by using the correlation between a component,which configures the service included in the PLP, and a service.

The third embodiment of the present invention is similar to the secondembodiment of the present invention. However, the third embodiment ofthe present invention corresponds to a signaling method enablinginformation associated with the component, which configures the sameservice, to be transmitted through a base PLP, and enabling the receiverto selectively receive a PLP, which configures the service desired bythe receiver, in the physical layer.

The fourth embodiment of the present invention corresponds to asignaling method respective to a case when the broadcast signal is beingtransmitted in an IP format. In the signaling method according to thefourth embodiment of the present invention, the receiver may merge thecomponent being transmitted by the PLPs included in the same PLP group,by using a correlation between a service and a PLP, which transmits thecomponents being included in the service, and then the receiver mayrecover a service.

The signaling of L1 signaling information, L2 signaling information,PAT/PMT, and so on, respective to the correlation between the PLPs, theTSs (or IP streams), the service, and the components according to firstto fourth embodiments of the present invention may be performed by theinput pre-processor or input processor of the broadcasting signaltransmitting device (or transmitter), or may be performed by the BICMmodule.

According to an embodiment of the present invention, when the inputstream corresponds to a TS stream, the input pre-processor of FIG. 7 mayperform signaling of the L1 signaling information and L2 signalinginformation and may generate PLPs including PAT/PMT and component PLPsconfiguring a service. Herein, the L2 signaling information may includeNIT, SDT, and so on.

According to another embodiment of the present invention, when the inputstream corresponds to a TS stream, the input pre-processor shown in FIG.11 may perform signaling of the L1 signaling information and L2signaling information, and may generate PLPS including ESG, providerinformation, bootstrap information, and so on, and component PLPsconfiguring a service. Herein, the L2 signaling information may an IPinformation table.

According to yet another embodiment of the present invention, signalingof the L1 signaling information, shown in FIG. 46 to FIG. 48, may beperformed by an L1 signaling generator included in the input processoror an L1 signaling generator included in the BICM module.

At this point, PLPs generated from the input pre-processor may beencoded by using the MISO method and then transmitted, or may be encodedby using the MIMO method and then transmitted. In the present invention,the PLP data being transmitted by using the MISO method may be referredto as MISO PLP data, and the PLP data being transmitted by using theMIMO method may be referred to as MIMO PLP data. According to theembodiment of the present invention, the MIMO PLP data may be processedwith MIMO encoding by the MIMO encoder of the BICM module shown in FIG.17, and the MISO PLP data may be processed with MISO encoding by theMISO encoder of the OFDM generator shown in FIG. 17. Additionally,according to the embodiment of the present invention, the L1 signalinginformation may also be processed with MISO encoding by the MISO encoderof the OFDM generator shown in FIG. 19.

Meanwhile, according to an embodiment of the present invention, in thebroadcasting signal receiving device (also referred to as a receiver),decoding may be performed on PLPs including L1/L2 signaling informationhaving the correlation between the PLP, TS (or IP stream), service,components signaled thereto, PAT/PMT or ESG, provider information,bootstrap information, and so on, and on PLPs including components byany one of a frame demapper, BICM decoder, output processor of FIG. 31to FIG. 34.

At this point, according to the embodiment of the present invention, theMISO PLP data, which are MISO encoded and received, may be MISO decodedby the OFDM demodulator of FIG. 28, and the MIMO PLP data, which areMIMO encoded and received, may be MIMO decoded by the BICM decoder of32. Additionally, according to the embodiment of the present invention,the L1 signaling information may be MISO decoded by the MISO decoder ofthe OFDM demodulator of FIG. 28. And, the process of selecting any oneof the MISO PLP data and the MIMO PLP data and performing decoding onthe selected PLP data may vary depending upon the first to fourthembodiments of the present invention. More specifically, according toany one of the first to fourth embodiments of the present invention, thepresent invention may be capable of knowing the PLPs in which thecomponents configuring a service are included. As a result, the PLPsconfiguring a specific service may be selected and outputted from theframe demapper of FIG. 31, and the selected and outputted PLPs may beprocessed with error correction decoding by the BICM Decoder of FIG. 32,thereby being merged as a single service by the output processor of FIG.34.

According to another embodiment of the present invention, when the inputstream corresponds to a TS format, the broadcasting signal receivingdevice of FIG. 35 may perform the above-described process. Morespecifically, any one of the frame demapper (210200), the PLPdeinterleaving and demodulator module (210500), the L1 decoder (210300),the BBF decoder and null packet reconstruction module (210600) mayperform decoding on the PLPs including L1/L2 signaling informationhaving the correlation between the PLP, TS, service, and componentssignaled thereto, and on PLPs including components. Most particularly,according to the embodiment of the present invention, in the presentinvention, the L1 decoder (210300) decodes the PLP including L1/L2signaling information having the correlation between the PLP, TS,service, and components signaled thereto and also including PAT/PMT,and, based upon the decoding result of the L1 decoder (210300), the PLPselecting module (210400) control the frame demapper (210200) so thatonly the PLPs of the components configuring the specific service can beoutputted from the frame demapper (210200). The PLPs that are selectedand outputted from the frame demapper (210200) pass through therespective PLP deinterleaving and demodulator module and the respectiveBBF decoder and null packet reconstruction module, so as to be merged toa single service in the TS merger. In the present invention, the PLPtransmitting the PSI/SI and, more particularly, the PAT/PMT will bereferred to as a base PLP.

According to yet another embodiment of the present invention, when theinput stream corresponds to an IP stream format, the broadcasting signalreceiving device of FIG. 36 may perform the above-described process.More specifically, any one of the frame demapper (220200), the PLPdeinterleaving and demodulator module (220500), the L1 decoder (220300),and the BBF decoder (220600) may perform decoding on the PLPs includingL1/L2 signaling information having the correlation between the PLP, IPstream, service, and components signaled thereto, ESG, bootstrapinformation, provider information, and so on, and on PLPs includingcomponents. Most particularly, according to the embodiment of thepresent invention, in the present invention, the L1 decoder (210300)decodes the PLP including L1/L2 signaling information having thecorrelation between the PLP, IP stream, service, and components signaledthereto and also including ESG, bootstrap information, providerinformation, and so on, and, based upon the decoding result of the L1decoder (220300), the PLP selecting module (220400) control the framedemapper (220200) so that only the PLPs of the components configuringthe specific service can be outputted from the frame demapper (220200).The PLPs that are selected and outputted from the frame demapper(220200) pass through the respective PLP deinterleaving and demodulatormodule and the respective BBF decoder, thereby being outputted to therespective buffer. The description presented above may be applied to atleast one of the first to fourth embodiments of the present invention,which are presented below.

Hereinafter, each embodiment will be described in more detail.

First Embodiment FIG. 49 to FIG. 51

FIG. 49 illustrates a conceptual diagram of a correlation between aservice according to the first embodiment of the present invention and aPLP group.

In case of transmitting a broadcast signal of a TS format, the firstembodiment of the present invention corresponds to a signaling methodfor recovering a transport stream of a single service by acquiring aservice ID from the receiver, by using a PLP group ID associated to theacquired service ID, and by merging multiple PLPs being included in thesame PLP group.

As shown in FIG. 49, the L1 signaling information region (500100)according to the first embodiment of the present invention may includeinformation related to each of the multiple PLPs, i.e., a PLP_GROUP_IDfield, a PLP_ID field, and so on, as shown in FIG. 46 to FIG. 48. Also,the L2 signaling information region (500200) may include an NIT and anSDT.

The NIT may include a PLP_GROUP_ID field, which is identical to thePLP_GROUP_ID field included in the L1 signaling information region(500100), and a transport_stream_id field. By using these fields, thereceiver may be capable of knowing to which PLP group a specifictransport stream is correlated. Also, the SDT may include atransport_stream_id field, which is identical to the transport_stream_idincluded in the NIT, and a service_id field. By using these fields, thereceiver may be capable of differentiating (or identifying) each of theservices being transmitted through a specific transport stream.

Eventually, among the many services included in a specific transportstream, the receiver may identify the desired service by using theservice_id field, which is included in the SDT. And, by using thetransport_stream_id field and the PLP_GROUP_ID field, which are includedin the NIT, the receiver may identify a PLP group, which is related withthe specific transport stream. Thereafter, the receiver may receive aPLP having the same PLP_GROUP_ID field, which is included in the L1signaling information region (500100). More specifically, the receivermay merge multiple PLPs, which are included in a PLP group beingcorrelated with the desired service, so as to recover a transportstream.

In other words, the receiver acquires an identifier of a service, whichis selected by the user, from the service_id field of the SDT. And, bymapping the transport_stream_id field of the SDT and thetransport_stream_id field of the NIT, a group identifier of the PLPstransmitting the components of the selected service may be acquired fromthe PLP_GROUP_ID field of the NIT. Subsequently, by mapping thePLP_GROUP_ID field of the NIT and the PLP_GROUP_ID field of the L1signaling information, each PLP identifier included in the PLP group maybe acquired from the PLP_ID field of the corresponding PLP. Thereafter,when the PLPS of the acquired PLP identifiers are merged, a TSconfiguring a service may be recovered.

Hereinafter, the fields, the NIT, and the SDT being included in the L1signaling information region (500100) according to the first embodimentof the present invention will be described in detail.

Since the L1 signaling information region (500100) according to thefirst embodiment of the present invention includes the same fields,which are described with reference to FIG. 46 to FIG. 48, the detaileddescription of the same will be omitted for simplicity.

The NIT corresponds to a table transmitting information related to thephysical structure of a multiplexer/transport stream being transmittedthrough the network, and diverse information respective to thecharacteristics of the network itself. The receiver may gain informationon the transport stream from the NIT.

The NIT according to the first embodiment of the present invention mayinclude a network_id field, a transport_stream_id field, and adelivery_system_descriptor loop.

Hereinafter, each field included in the NIT shown in FIG. 49 will bedescribed in detail.

The network_id field is used for identifying a network through which thecurrent broadcast signal is being transmitted.

The transport_stream_id field is used for identifying a transport streamthat is currently being transmitted.

The delivery_system_descriptor may include fields required (ornecessary) for matching the transport stream with the PLP and thetransmitting system. Most particularly, the delivery_system_descriptoraccording to the present invention may include a PLP_GROUP_ID field thatis identical to the PLP_GROUP_ID field included in the L1 signalinginformation.

Furthermore, the delivery_system_descriptor may include a system_idfield, system_parameter( ) field and a cell_parameter( ) field.

A system_id field is used for identifying a system that is unique to thebroadcast network performing transmission.

A system_parameters( ) field may include parameters indicating thetransmitting system characteristics, such as whether the communicationis performed in a SISO/MIMO mode, a bandwidth, a guard interval, atransmission mode, and so on.

A cell_parameters( ) field may include parameters indicating cellinformation, such as a center frequency, a cell identifier, and so on.

The SDT corresponds to a table including information on multipleservices, which are included in a single transport stream. The SDTaccording to the first embodiment of the present invention may include atransport_stream_id field, and a service loop. And, the service loop mayinclude a service_id field and is repeated as many times as the numberof services included in a transmission frame.

Hereinafter, each field included in the SDT shown in FIG. 49 will bedescribed in detail.

Since the transport_stream_id field is identical to thetransport_stream_id field, which is included in the NIT, a detaileddescription of the same will be omitted for simplicity. The service_idfield is used for identifying multiple services included in thetransmission frame.

FIG. 50 shows a delivery_system_descriptor field of the NIT of FIG. 49according to the first embodiment of the present invention. Herein, thedelivery_system_descriptor field is used for connecting the PLP_GROUP_IDfield of the L1 signaling information region 500100 to the transportstream.

As shown in FIG. 50, the delivery_system_descriptor may include adescriptor_tag field, a descriptor_length field, a system_id field, aPLP_GROUP_ID field, and a first loop.

The first loop is used when the descriptor_length field has a sizelarger than 3. And, in this case, the first loop may include asystem_parameters( ) field and a second loop.

The second loop may include a cell_parameters( ) field.

Hereinafter, each field will be described in detail.

The descriptor_tag field is used for identifying each descriptor.

The descriptor_length field is used for indicating a total length of thedata portion of each descriptor.

The system_id field is used for identifying a system that is unique tothe broadcast network performing transmission.

The PLP_GROUP_ID field may identify a PLP group that is to be matchedand merged with the transport_stream_id field. Since the essentialdetails of the PLP_GROUP_ID field are identical to those of thePLP_GROUP_ID field shown in FIG. 34, a detailed description of the samewill be omitted for simplicity.

Since the system_parameters( ) field included in the first loop and thecell_parameters( ) field included in the second loop are identical tothose described in FIG. 49, a detailed description of the same will beomitted for simplicity.

FIG. 51 illustrates a flow chart showing the process steps of a servicescanning method of the receiver according to the first embodiment of thepresent invention.

The receiver receives a TP type broadcast signal transmitted in aspecific channel through tuning (S507100). In this case, in order toreceive a service desired by the user, the receiver requires informationon the service included in the transmission frame, which is beingtransmitted through the respective channel. Although this process stepis not shown in the drawing, this process step may be performed by thetuner of the receiver and may be modified or varied in accordance withthe intentions of the system designer.

Then, the receiver may decode the L1 signaling information included inthe transmission frame, so as to acquire a PLP ID, a PLP Group ID, and asystem ID, which are included in the transmission frame (S507200).Thereafter, the receiver may identify the PLP groups by using thedecoded PLP Group ID, so as to select the desired PLP group, and maydecode the PLP including the L2 signaling information and the PSI/SI(S507300). The receiver may decode the NIT and the SDT included in thedecoded L1 signal information, and the receiver may also decode aPAT/PMT included in the PLP, thereby being capable of storing serviceinformation associated with the transmitting system and the PLPstructure (S507400). The service information according to the presentinvention may include a service ID for identifying a service.

Subsequently, the receiver may determine whether or not the currentlyselected PLP group corresponds to the last PLP group (S507500).

Based upon the determined result, when it is determined that theselected PLP group does not correspond to the last PLP group, thereceiver may return to the process step S507300, so as to select thenext PLP group. Alternatively, when it is determined that the selectedPLP group corresponds to the last PLP group, the receiver may determinewhether or not the current channel corresponds to the last channel(S507600).

Then, based upon the determined result, when it is determined that thecurrent channel does not correspond to the last channel, the receivermay return to the process step S507100, so as to tune to the nextchannel. And, alternatively, when it is determined that the currentchannel corresponds to the last channel, the receiver may use the storedservice information so as to tune to a first service or a pre-setservice (S507700).

If the broadcasting signal receiving device has the same structure asFIG. 27 or FIG. 47, as described above, the decoding of the PLPsincluding the L1 signaling information, the L2 signaling information,the PLPs transmitting the PSI/SI, and the PLPs including components maybe performed by at least one of the frame demapper, the BICM decoder,and the output processor. If the broadcasting signal receiving devicehas the same structure as FIG. 35, the decoding of the PLPs includingthe L1 signaling information, the L2 signaling information, the PLPstransmitting the PSI/SI, and the PLPs transmitting components may beperformed by at least one of the frame demapper, the PLP deinterleavingand demodulator module, the L1 decoder, the BBF decoder, and the nullpacket reconfigurating module. Also, the scanning process may beperformed by a separate controller.

Second Embodiment FIG. 52 to FIG. 54

FIG. 52 illustrates a conceptual diagram of a correlation between aservice according to the second embodiment of the present invention anda PLP group.

The first embodiment of the present invention corresponds to a signalingmethod using a PLP Group ID and a service ID. And, in this case, thereceiver may use a correlation between a service and a PLP group one aservice level, so as to recover a service.

However, depending upon the characteristics of the receiver, when dataof an enhancement layer is to be selectively decoded so as to provide ahigh picture quality image, the signaling method according to the firstembodiment of the present invention is disadvantageous in that theinformation on a video stream, which is included in the PLP, cannot beacquired.

Therefore, according to the second embodiment of the present invention,when receiving a TS format broadcast signal, in addition to thesignaling method using the correlation between a service and a PLPgroup, a signaling method that can determine the type of the currenttransport stream and that can acquire information related to thecomponents included in each PLP, thereby being capable of selectivelyreceiving the transport stream and the PLP based upon the acquiredinformation.

As shown in FIG. 52, the L1 signaling information region 508100according to the second embodiment of the present invention may includediverse information related to each of the multiple PLPs, i.e., aPLP_GROUP ID field, a PLP_ID field, a PLP_COMPONENT_TYPE field, and soon. Also, the L2 signaling information region field 508200 may includean NIT and an SDT. Herein, the NIT may include a PLP_GROUP_ID field,which is identical to the PLP_GROUP_ID field included in the L1signaling information region 508100, and a transport_stream_id field. Byusing these fields, the receiver may be capable of knowing to which PLPgroup a specific transport stream is correlated. Also, the SDT mayinclude a transport_stream_id field, which is identical to thetransport_stream_id included in the NIT, and a service_id field. Byusing these fields, the receiver may be capable of differentiating (oridentifying) each of the services being transmitted through a specifictransport stream. Additionally, since the PMT include a program_numberfield, which matches with the service_id field included in the SDT, thereceiver may use the program_number field so as to verify a programnumber included in the selected service. Moreover, since the PMTincludes a stream type field, a PLP_ID field, and a PLP_COMPONENT_TYPEfield, the receiver may determine the type of the current stream byusing the stream type field. And, by using the PLP_COMPONENT_TYPE field,the receiver may determine the type of the component included in thecurrent PLP, so as to selectively receive the PLP.

Eventually, as described in the first embodiment of the presentinvention, the receiver may acquire the service_id field from the SDT,so as to be capable of identifying a desired service, among a pluralityof services included in a transmission frame. Then, by using the NIT,the receiver may identify a PLP group, which is related to a specifictransport stream transmitting the service. Thereafter, the receiver mayreceive a PLP having a PLP_GROUP_ID field included in the L1 signalinginformation, thereby being capable of recovering a service stream.Additionally, the receiver may also use the component informationincluded in the PLP, so as to selectively receive the PLP and to becapable of providing an image best-fitting the receiver characteristic.

Hereinafter, the fields, the NIT, and the SDT being included in the L1signaling information according to the second embodiment of the presentinvention will be described in detail.

Since the L1 signaling information according to the second embodiment ofthe present invention includes the same fields, which are included inthe L1 signaling information region described with reference to FIG. 46to FIG. 48, and since the NIT and the SDT are identical to the NIT andSDT described with reference to FIG. 49, detailed description of thesame will be omitted for simplicity. The PMT corresponds to a tableincluding information indicating or identifying the types of the streamsbeing included in each service or PID information for identifying thestreams.

The PMT according to the second embodiment of the present invention maybe transmitted through a PLP, and the transmitting end may process andtransmit the PMT as data. Furthermore, the PMT may also include aprogram_number field, and a PID loop.

Hereinafter, each field included in the PMT shown in FIG. 52 will bedescribed in detail.

A program_number field is used for identifying each program (or service)within the current transport stream. Herein, the program_number field ismatched with the service_id field of the SDT. The PID loop may includePID information (elementary_PID) of a TS packet to which individual bitstreams, such as video, audio, and so on, are being transmitted, whereinthe individual bit streams configure a program or (service), astream_type field, and a component_id_descriptor. Herein, the PIDinformation is a PID of a TS packet transmitting each stream, such asvideo, audio, and so on, configuring a program (or service). Astream_type field represents encoding information and a type of an ESwhich is included in a TS packet having a PID value that is expressed inthe elementary_PID field. Examples of the streams types according to thepresent invention may include an SVC stream, an AVC stream, and so on.

An elementary_PID field represents an identifier of an ES (ElementaryStream). That is, it is a field used for identifying a TS packettransmitting the ES.

A component_id_descriptor may include a PLP_ID field and aPLP_COMPONENT_TYPE field. Herein, since the PLP_ID field and thePLP_COMPONENT_TYPE field are identical to the PLP_ID field and thePLP_COMPONENT_TYPE field, which are included in the L1 signaling, adetailed description of the same will be omitted for simplicity.

Therefore, when multiple stream types exist, the receiver may identify aspecific stream by using the stream_type field and may select theidentified stream. Also, by using the PLP_COMPONENT_TYPE field, thereceiver may also determine whether the component being transmitted bythe PLP corresponds to a base layer or an enhancement layer, and thereceiver may then selectively decode the PLP of the enhancement layer inaccordance with the receiver characteristic.

FIG. 53 corresponds to an exemplary component_id_descriptor, which isincluded in FIG. 52. Herein, the component_id_descriptor field is beingused for connecting the PLP_COMPONENT_TYPE field of the L1 signalinginformation region 508100 to the transport stream.

The component_id_descriptor may include a descriptor_tag field, adescriptor_length field, a system_id field, a PLP_ID field, and aPLP_COMPONENT_TYPE field. Herein, the PLP_ID field is used foridentifying a PLP that matches with a PID sub stream of thecorresponding stream type.

Since the contents of each field are identical to those described inFIG. 47 and FIG. 50, detailed description of the same will be omittedfor simplicity.

FIG. 54 illustrates a flow chart showing a service scanning method ofthe receiver according to a second embodiment of the present invention.

The receiver receives a broadcasting signal having a TS format and beingtransmitted to a specific channel via tuning (S510100). In this case, inorder to receive a service that is wanted (or desired) by the user,diverse information that can identify the service included in thetransmission frame, which is being transmitted through the channel, isrequired. Although this process is not shown in the drawing, thecorresponding process may be performed by the tuner of the receiver andmay be modified and varied in accordance with the intentions of thesystem designer.

Then, the receiver may decode the L1 signaling information included inthe transmission frame, so as to acquire a PLP ID, a PLP Group ID, and asystem ID, which are included in the transmission frame (S510200).Thereafter, the receiver may identify the PLP groups by using thedecoded PLP Group ID, so as to select the desired PLP group, and maydecode the PLP including the L2 signaling information and the PSI/SI(S510300). The receiver may decode the NIT and the SDT included in thedecoded L1 signal information, and the receiver may also decode aPAT/PMT included in the PLP, thereby being capable of storing serviceinformation associated with information on the structures of thetransmitting system and the PLP (S510400). The service informationaccording to the present invention may include a service ID foridentifying a service.

Additionally, the receiver may use the stream_type field and thePLP_COMPONENT_TYPE field included in the decoded PMT, so as to verifythe type of the component being transmitted by the current PLP, and thenthe receiver may store the component that is to be additionally receivedin accordance with the receiver characteristics (S510500). Morespecifically, the receiver may use the above-described stream_type andPLP_component_type information, so as to additionally receiver/store acomponent corresponding to the service, which may be provided inaccordance with the receiver characteristic.

Subsequently, the receiver may determine whether or not the currentlyselected PLP group corresponds to the last PLP group (S510600).

Based upon the determined result, when it is determined that theselected PLP group does not correspond to the last PLP group, thereceiver may return to the process step S510300, so as to select thenext PLP group. Alternatively, when it is determined that the selectedPLP group corresponds to the last PLP group, the receiver may determinewhether or not the current channel corresponds to the last channel(S510600).

Then, based upon the determined result, when it is determined that thecurrent channel does not correspond to the last channel, the receivermay return to the process step S510100, so as to tune to the nextchannel. And, alternatively, when it is determined that the currentchannel corresponds to the last channel, the receiver may use the storedservice information so as to tune to a first service or a pre-setservice (S510700).

If the broadcasting signal receiving device has the same structure asFIG. 27 or FIG. 47, as described above, the decoding of the PLPsincluding the L1 signaling information, the L2 signaling information,the PLPs transmitting the PSI/SI, and the PLPs including components maybe performed by at least one of the frame demapper, the BICM decoder,and the output processor. If the broadcasting signal receiving devicehas the same structure as FIG. 35, the decoding of the PLPs includingthe L1 signaling information, the L2 signaling information, the PLPstransmitting the PSI/SI, and the PLPs transmitting components may beperformed by at least one of the frame demapper, the PLP deinterleavingand demodulator module, the L1 decoder, the BBF decoder, and the nullpacket reconfigurating module. Also, the scanning process may beperformed by a separate controller.

Third Embodiment FIG. 55 to FIG. 59

FIG. 55 illustrates a conceptual diagram of a correlation between aservice according to the third embodiment of the present invention and aPLP group.

When a channel is scanned by the receiver according to the secondembodiment of the present invention, the receiver may not be capable ofscanning (or searching through) the entire PLP, which transmits thecomponents included in a single service. Since the components includedin each of the multiple services are transmitted through each PLP, a PLPthat does not include PSI/SI may also exist.

Therefore, in the third embodiment of the present invention, PSI/SI,such as the PAT/PMT, may be transmitted to a random PLP included in themultiple PLP regions, so that the entire PLP transmitting the componentsincluded in a single service can be scanned (or searched). As describedabove, in the description of the present invention, the PLP transmittingservice configuration information, such as the PAT/PMT, may also bereferred to as a base PLP. More specifically, when the receiver decodesthe base PLP, information on the remaining component PLPs included in asingle service may be acquired.

Eventually, according to the third embodiment of the present invention,instead of acquiring signaling information by processing all of the TS,by processing signaling information of the physical layer and byacquiring signaling information included in the base PLP, the signalinginformation respective to each PLP may be acquired.

As shown in FIG. 55, the L1 signaling information region 511100according to the third embodiment of the present invention may includeinformation respective to each of the multiple PLPs, i.e., a PLP_GROUPID field, a PLP_ID field, a PLP_COMPONENT_TYPE field, a PLP_PROFILEfield, and so on. Additionally, the L2 signaling information region511200 may include an NIT and an SDT. Herein, the NIT may include aBASE_PLP_ID field, which is matched with the PLP_ID field being includedin the L1 signaling information region 511100. And, by using theBASE_PLP_ID field, the receiver may identify a base PLP, which transmitsthe PMT/PAT. Furthermore, the SDT may include a transport_stream_idfield, which is identical to the transport_stream_id included in theNIT, and a service_id field. And, by using the SDT, the receiver maydifferentiate each of the services being transmitted through a specifictransport stream.

Additionally, since the PMT being transmitted through the base PLPinclude a program_number field, which is matched with the service_idfield included in the SDT, by using the program_number field, thereceiver may verify the program number included in the selected service.In addition, the PMT may include a stream_type field, a PLP_ID field,and a PLP_PROFILE field. In this case, by referring to the stream typefield included in the PMT, the receiver may recognize the type of thecurrent stream, and by using the PLP_ID field and the PLP_PROFILE filed,the receiver may determine the correlation between the PLP and thecomponent, thereby being capable of decoding the PLP best-fitting thePLP. More specifically, the receiver may use the PLP_PROFILE fieldincluded in the PMT, so as to perform decoding on the PLP, whichtransmits a distinguished service component, such as a standard picturequality service, high picture quality service, and so on, in accordancewith the characteristics of the receiver. Thus, the TS best-fitting thereceiver characteristics may be recovered.

Eventually, the receiver may identify and select the base PLP by usingthe BASE_PLP_ID field, which is included in the NIT, and the receivermay decode a PMT, which is transmitted through the base PLP.Additionally, the receiver may identify and select a wanted (or desired)service by using the service_id field, which is included in the SDT.Moreover, in addition to being capable of decoding all of the PLPs thatare included in a component, which is included in a single service, byusing the PLP_PROFILE field, the receiver may decode a PLP in accordancewith the receiver characteristic.

Hereinafter, the L1 signaling information region (511100), the NIT, theSDT, and the PMT according to the third embodiment of the presentinvention will be described in detail.

Since the L1 signaling information according to the third embodiment ofthe present invention is identical to the L1 signaling information shownin FIG. 46 to FIG. 48, a detailed description of the same will beomitted for simplicity.

The PLP_PROFILE field may identify whether the corresponding PLP is amandatory (or required) PLP or an optional (or selective) PLP. Forexample, in case the component being transmitted through the PLP isidentified (or distinguished) as a base layer or an enhancement layer,the PLP transmitting the base layer becomes the mandatory PLP, and thePLP transmitting the enhancement layer becomes the optional PLP.Particularly, the base PLP becomes the mandatory PLP. More specifically,depending upon the receiver characteristic, such as a mobile receiver, afixed-type receiver, and so on, the receiver may use the PLP_PROFILEfield so as to verify by which receiver the component of the broadcastservice being transmitted to the current PLP may be used, and dependingupon the receiver characteristic, the receiver may determine whether ornot to decode the current PLP.

The NIT according to the third embodiment of the present invention issimilar to the NIT according to the second embodiment of the presentinvention, which is described above with reference to FIG. 52. However,unlike the NIT according to the second embodiment of the presentinvention, the NIT according to the third embodiment of the presentinvention may further include a BASE_PLP_ID field.

Herein, the BASE_PLP_ID field is used for identifying the base PLP. And,the base PLP may transmit PSI/SI information of a corresponding service,such as the PMT/PAT. Additionally, the BASE_PLP_ID field may be includedin a delivery_system_descriptor of the NIT.

The PMT according to the third embodiment of the present invention mayinclude a program_number field and a PID loop. And, the PID loop mayinclude a stream_type field and a component_id_descriptor. Herein, thecomponent_id_descriptor may include a PLP_PROFILE field and a PLP_IDfield. The contents of the program_number field and the PLP_ID field areidentical to those described above with reference to FIG. 47 and FIG.52. And, since the PLP_PROFILE field is identical to the PLP_PROFILEfield included in the L1 signaling information, a detailed descriptionof the same will be omitted for simplicity.

FIG. 56 illustrates an exemplary delivery system descriptor included inthe NIT of FIG. 55.

As shown in FIG. 56, the delivery_system_descriptor according to thethird embodiment of the present invention is identical to thedelivery_system_descriptor according to the first embodiment of thepresent invention, which is shown in FIG. 50. However, unlike thedelivery_system_descriptor according to the first embodiment of thepresent invention, the delivery_system_descriptor according to the thirdembodiment of the present invention may further include a BASE_PLP_IDfield. Since the description of the BASE_PLP_ID field is identical tothat of FIG. 55, a detailed description of the same will be omitted forsimplicity.

FIG. 57 illustrates an exemplary component ID descriptor included in thePMT of FIG. 55.

As shown in FIG. 57, the component_id_descriptor, which is included inthe PID loop of the PMT according to the third embodiment of thepresent, is identical to the component_id_descriptor according to thesecond embodiment of the present invention, which is shown in FIG. 52.However, the component_id_descriptor according to the third embodimentof the present invention may include a PLP_PROFILE field instead of thePLP_COMPONENT_TYPE field. Herein, since the description of thePLP_PROFILE field is identical to that of FIG. 55, a detaileddescription of the same will be omitted for simplicity.

FIG. 58 illustrates an exemplary PLP_PROFILE field according to thethird embodiment of the present invention.

As shown in FIG. 58, the PLP_PROFILE field may provide information in abit-unit selector format.

The PLP_PROFILE field may indicate information on a video component inaccordance with the field value. For example, when the field value isequal to 0x00, this signifies a common profile and indicates that thevideo component corresponds to a component that can be received and usedby any receiver. When the field value is equal to 0x01, this indicatesthat the video component corresponds to a component that can be usedonly by mobile receivers, and when the field value is equal to 0x02,this indicates that the video component corresponds to an HD profilecomponent that can be used only by HD receivers (or fixed receivers).And, when the field value is equal to 0x03, this indicates that thecomponent can be applied to both mobile receivers and HD receivers.

FIG. 59 illustrates a flow chart showing the process steps of a servicescanning method of the receiver according to the third embodiment of thepresent invention.

The receiver receives a broadcasting signal having a TS format viatuning (S515100). In this case, in order to receive a service that iswanted (or desired) by the user, diverse information that can identifythe service included in the transmission frame, which is beingtransmitted through the channel, is required. Although this process isnot shown in the drawing, the corresponding process may be performed bythe tuner of the receiver and may be modified and varied in accordancewith the intentions of the system designer.

The receiver decodes the L1 signaling information included in thetransmission frame, so as to acquire a PLP ID, a PLP group ID, PLPcomponent type information, PLP profile information, system ID, and soon (S515150). Thereafter, the receiver identifies the PLP groups basedupon the decoded PLP group ID, so as to select a wanted (or desired) PLPgroup, and then decodes the L2 signaling information (S515200).Additionally, the receiver decodes the NIT included in the L2 signalinginformation and uses the BASE_PLP_ID field included in the NIT, so as tofind and locate the base PLP of each service (S515250). Subsequently,the receiver may use the transport_stream_id field, which is included inthe NIT, so as to identify the transport stream included in the PLPgroup and to decode the PMT included in the base PLP (S515300). Thereceiver may use the PLP_PROFILE field, which is included in a componentID descriptor field of the decoded PMT, so as to verify which receivermay use the component of the broadcast service, which is beingtransmitted to the current PLP in accordance with the receivercharacteristic, such as mobile receiver, HD receiver, and so on.Accordingly, by using the PLP_ID field, the receiver may selectivelydecode the PLP that is requested to be decoded.

Thereafter, the receiver may store the information related to thecorrelation between the component and the PLP, based upon the receivercharacteristic (S515350). The information related to the correlationbetween the component and the PLP may include the PID information of thePMT and the PLP_id included in the component_ID_descriptor.

Subsequently, the receiver may determine whether or not the current TScorresponds to the last TS within the PLP group (S515400).

When it is determined that the current TS does not correspond to thelast TS, the receiver may return to the process step S515250, so as toparse the NIT and to acquire the base PLP by using the BASE_PLP_IDfield. Alternatively, when it is determined that the current TScorresponds to the last TS, the receiver may determine whether or notthe current PLP group corresponds to the last PLP group (S515450).

When it is determined that the selected PLP group does not correspond tothe last PLP group, the receiver may return to the process step S515200,so as to select the next PLP group and to decode a base PLP.Alternatively, when it is determined that the selected PLP groupcorresponds to the last PLP group, the receiver may determine whether ornot the current channel corresponds to the last channel (S515500).

Thereafter, when it is determined that the current channel does notcorrespond to the last channel, the receiver may return to the processstep S515100, so as to tune to the next channel. And, alternatively,when it is determined that the current channel corresponds to the lastchannel, the receiver may tune to a first service or a pre-set service(S515550).

If the broadcasting signal receiving device has the same structure asFIG. 27 or FIG. 47, as described above, the decoding of the PLPsincluding the L1 signaling information, the L2 signaling information,the PLPs transmitting the PSI/SI, and the PLPs including components maybe performed by at least one of the frame demapper, the BICM decoder,and the output processor. If the broadcasting signal receiving devicehas the same structure as FIG. 35, the decoding of the PLPs includingthe L1 signaling information, the L2 signaling information, the PLPstransmitting the PSI/SI, and the PLPs transmitting components may beperformed by at least one of the frame demapper, the PLP deinterleavingand demodulator module, the L1 decoder, the BBF decoder, and the nullpacket reconfigurating module. Also, the scanning process may beperformed by a separate controller.

Fourth Embodiment FIG. 60 to FIG. 62

FIG. 60 illustrates a conceptual diagram of a correlation between aservice according to the fourth embodiment of the present invention anda PLP group.

In case of transmitting a broadcast signal of a IP format, the fourthembodiment of the present invention corresponds to a signaling methodfor recovering a transport stream by acquiring a service IP address andinformation on a component type and information on a component address,which are included in a PLP, and by merging multiple PLPs being includedin the same PLP group.

As shown in FIG. 60, the L1 signaling information region 516100according to the fourth embodiment of the present invention may includeinformation related to each of the multiple PLPs, i.e., a PLP_GROUP IDfield, a PLP_ID field, and so on. Also, the L2 signaling informationregion 516200 may include an IP information table, and the IPinformation table may include a IP_address_list( ) field and adescriptor. The IP_address_list( ) field may include IP addressinformation for receiving a Bootstrap, and the descriptor may includethe same PLP_GROUP_ID field and PLP_ID field that are included in the L1signaling information region 516100. Since the IP_address_list( ) fieldand the descriptor form a pair, by using this pair, the receiver may becapable of knowing which PLP group is correlated to a specific IPstream. Thereafter, the receiver may use the IP_address_list( ) field,so as to receive Bootstrap information. Herein, the bootstrapinformation includes a boot_IP_address field. And, by using theboot_IP_address field, the receiver may acquire an IP address that canreceiver (or acquire) a service guide information or broadcast contentguide information.

Subsequently, by using the received bootstrap information, the receivermay receiver service guide information, such as ESG (Electronic ServiceGuide)/BCG (Broadcast Contents Guide). The service guide information orbroadcast contents guide information may be transmitted through aninteractive channel and may be received through an IP stream, which isincluded in a specific PLP. This may vary depending upon the intentionsof the system designer. The receiver may use the service_id field, thecomponent_type field, and the component_IP_address field, which areincluded in the ESG/BCG, so as to decode a desired (or wanted) serviceand service components.

Eventually, by using the component_IP_address included in the ESG/BCG,or by using the boot_IP_address field of the bootstrap, the receiver mayacquire an IP address for each service and service components. And, byusing the IP_address_list( ) field and the PLP_GROUP_ID field of the IPinformation table, the receiver may be capable of knowing which IPstream/packet is correlated to the PLP group. Thereafter, the receivermay merge the service components that are included in a PLP having thesame PLP_GROUP_ID field included in the L1 signaling information region516100, so as to recover a service.

Hereinafter, the L1 signaling information, the IP information table, abootstrap, and an ESG/BCG will be described in detail.

The L1 signaling information according to the fourth embodiment of thepresent invention may include the same fields included in the L1signaling information, which is described in FIG. 46 to FIG. 48. And,the receiver may use the PLP_COMPONENT_TYPE field so as to determinewhether or not the L1 signaling information is matched with thecomponent_type field included in the ESG/BCG.

The IP information table according to the fourth embodiment of thepresent invention corresponds to a table include IP-related information,i.e., information on an IP address and so on. Herein, the receiver maybe capable of knowing how the IP stream is being transmitted from the IPinformation table through the transport stream.

The IP information table may include an IP_addr_location loop, and theIP_addr_location loop may include a target_IP_add_descriptor( ) and anIP/MAC_location_descriptor.

The target_IP_add_descriptor( ) may include an IP_address_list( ) field,and the IP_address_list( ) field may include information related to theIP address. According to the embodiment of the present invention, thepresent invention includes an IP address/port field. Depending upon thenumber of ports, a plurality of the IP address/port fields may beincluded. The IP/MAC_location_descriptor may also be referred to as anIP/MAC_location_information field, which may be used for connecting thePLP_COMPONENT_TYPE field included in the L1 signaling information to theIP stream. The IP/MAC_location_descriptor may include the same PLP_IDfield and PLP_GROUP_ID field as the PLP_ID field and the PLP_GROUP_IDfield, which are included in the L1 signaling information.

Hereinafter, each field included in the bootstrap and ESG/BCG shown inFIG. 60 will be described in detail.

Herein, the Bootstrap may include a boot_IP_addr field, and theboot_IP_addr field may identify a booting address of the IP.

The ESG/BCG may include a NUM_SERVICE loop. Herein, the NUM_SERVICE loopmay include a respective service_name field, service_id field, and aNUM_COMPONENT loop for each of the multiple services.

The service_name field may be used for indicating the name of eachservice, and the service_id field may be used for identifying eachservice.

The NUM_COMPONENT loop corresponds to a loop include information on themultiple components, which are included in a service. Herein, theNUM_COMPONENT loop may include a component_type field and acomponent_IP_address field.

The component_type field may be used for identifying component types ofthe service. And, examples of the components according to the presentinvention may include a video component of the base layer, a videocomponent of the enhancement layer, audio components, data components,and so on. Also, the component_type field may be matched with thePLP_COMPONENT_TYPE field, which is included in the L1 signalinginformation.

The component_IP_address field may identify the IP address of eachcomponent.

FIG. 61 illustrates an exemplary IP/MAC_location_descriptor according tothe fourth embodiment of the present invention.

As shown in FIG. 61, the IP/MAC_location_descriptor according to thefourth embodiment of the present invention may include the same fieldsas the component_id_descriptor field according to the second embodimentof the present invention, which is described above with reference toFIG. 53. Herein, however, the IP/MAC_location_descriptor according tothe fourth embodiment of the present invention may include aPLP_GROUP_ID field instead of the PLP_COMPONENT_TYPE field. Since thedescription of each field is identical to that of FIG. 47 and FIG. 53,detailed description of the same will be omitted for simplicity.

FIG. 62 illustrates a flow chart showing the process steps of a servicescanning method of the receiver according to the fourth embodiment ofthe present invention.

The receiver tunes to receive an IP type broadcast signal (S518100). Inthis case, in order to receive a service desired by the user, thereceiver requires information on the service included in thetransmission frame, which is being transmitted through the respectivechannel. Although this process step is not shown in the drawing, thisprocess step may be performed by the tuner of the receiver and may bemodified or varied in accordance with the intentions of the systemdesigner.

Then, the receiver may decode the L1 signaling information included inthe transmission frame, so as to acquire a PLP ID and a PLP Group ID(S518200). Thereafter, the receiver may identify the PLP groups by usingthe decoded PLP group ID so as to select a desired PLP group, and thereceiver may then decode the L2 signaling information and the PLPincluding the PSI/SI and metadata (S518300).

The receiver may decode the IP information table included in the decodedL2 signaling information, and the receiver may also decode the metadataincluded in the PLP (S518400). Additionally, the receiver may acquireservice information associated with information on the transmittingsystem and PLP structures, thereby being capable of storing the acquiredservice information (S518400). The service information according to thepresent invention may include a service IP address, a component IPaddress, and so on. Subsequently, the receiver may determine whether ornot the currently selected PLP group corresponds to the last PLP group(S518500).

Based upon the determined result, when it is determined that theselected PLP group does not correspond to the last PLP group, thereceiver may return to the process step S518300, so as to select thenext PLP group. Alternatively, when it is determined that the selectedPLP group corresponds to the last PLP group, the receiver may determinewhether or not the current channel corresponds to the last channel(S518600).

Then, based upon the determined result, when it is determined that thecurrent channel does not correspond to the last channel, the receivermay return to the process step S518100, so as to tune to the nextchannel. And, alternatively, when it is determined that the currentchannel corresponds to the last channel, the receiver may use the storedservice information so as to tune to a first service or a pre-setservice (S518700).

If the broadcasting signal receiving device has the same structure asFIG. 27 or FIG. 47, as described above, the decoding of the PLPsincluding the L1 signaling information, the L2 signaling information,the PLPs transmitting the PSI/SI and metadata, and the PLPs includingcomponents may be performed by at least one of the frame demapper, theBICM decoder, and the output processor. If the broadcasting signalreceiving device has the same structure as FIG. 36, the decoding of thePLPs including the L1 signaling information, the L2 signalinginformation, the PLPs transmitting the PSI/SI, and the PLPs transmittingcomponents may be performed by at least one of the frame demapper, thePLP deinterleaving and demodulator module, the L1 decoder, the BBFdecoder, and the null packet reconfigurating module. Also, the scanningprocess may be performed by a separate controller.

FIG. 63 illustrates a flow chart showing a method for receiving abroadcasting signal according to an embodiment of the present invention.First of all, a broadcasting signal is received (S600100). At thispoint, according to the embodiment of the present invention, thereceived broadcasting signal includes a transmission frame, and thetransmission frame includes a plurality of PLPs transmitting componentsconfiguring a broadcasting service, first and second signalinginformation having signaling information of the plurality of PLPssignaled thereto, a first preamble signal having a preamble formatsignaled thereto, and a second preamble signal having pilot patterninformation signaled thereto. Additionally, according to the embodimentof the present invention, one of the plurality of PLPs corresponds to abase PLP, which includes a program number corresponding to thebroadcasting service and program map table information havingidentification information of each PLP signaled thereto. The receptionof the broadcasting signal is performed by the tuner.

Herein, according to the embodiment of the present invention, the firstpreamble signal corresponds to the P1 signaling information, and thesecond preamble signal corresponds to the AP1 signaling information.

Additionally, according to the embodiment of the present invention, thefirst signaling information includes PLP group identificationinformation (PLP GROUP ID) for identifying a PLP group including theplurality of PLPs, and a PLP identification information (PLP ID) foridentifying each PLP, and the second signaling information includes basePLP identification information (BASE PLP ID) for identifying the basePLP, and service identification information (SERVICE ID) for identifyingthe broadcasting service. Herein, according to the embodiment of thepresent invention, the base PLP identification information is includedin the NIT of the second signaling information, and the serviceidentification information is included in the SDT of the secondsignaling information.

When the broadcasting signal is received in step S600100, the receivedbroadcasting signal is demodulated based upon first and second preamblesignals, which are included in the transmission frame of the receivedbroadcasting signal (S600200). Then, FEC decoding is performed on thedemodulated broadcasting signal (S600300). Thereafter, based upon thePMT and the first and second signaling information, which are includedin the base PLP, a PLP group including a plurality of PLPs is identifiedfrom the FEC decoded broadcasting signal, and at least one PLP of theidentified PLP group is decoded, so as to provide the broadcastingservice (S600400).

According to an embodiment of the present invention, in step S600400,the PLP group including the plurality of PLP is identified, and each PLPincluded in the identified PLP group is identified, by using the PLPgroup identification information and the identification information ofeach PLP

, which are included in the first signaling information. Also, accordingto the embodiment of the present invention, the base PLP and thebroadcasting service are identified by using the base PLP identificationinformation and the service identification information, which are bothincluded in the second signaling information. Moreover, according to theembodiment of the present invention, packet identifiers of the TSsincluded in the decoded PLP are acquired by using a program numberincluded in the PMT, which is acquired from the base PLP, PLPidentification information for identifying each PLP, component typeinformation indicating the type of the component included in each PLPtype, and so on. Herein, according to the embodiment of the presentinvention, the demodulation process is performed by the OFDMdemodulator, the FEC decoding process is performed by the FEC decoder ofthe BICM decoder, and the decoding process of the PLP is performed by atleast one of the frame demapper, the BICM decoder, and the outputprocessor.

Hereinafter, different embodiments are disclosed. Afterwards, theembodiments are described using different terms that correspond to theabove-used terms but have the same meanings. For example, the term, DP(data pipe), are used in same meanings as the term, PLP (physical layerpipe) that are already used above.

As a transmission data unit in physical layer, the term, DP (data pipe),and the term, PLP (physical layer pipe), may have the same meanings. Asone example, the terms, “data PLP” as is used above, hereinafter,correspond to the terms, “PLP (physical layer pipe) that carries servicedata”.

Thus, the type1 data PLP and type2 data PLP correspond to the type 1 DPand type 2 DP.

And, the terms, “L1 signaling information” are used in the same meaningas the terms, “physical layer signaling data (PLS data)”. Because thephysical layer may be called as L1 layer in this art, the two terms maybe used as an identical concept.

As an example of the above terms, the terms, “L1-pre-signalinginformation” may be called “PLS-pre information” hereinafter and the twoterms means a physical signaling data part which carries basicinformation about the transmitting system as well as the parametersneeded to decode another physical signaling part followingL1-pre-signaling information (or PLS-pre information).

Similarly, the terms “L1-post configurable signaling information” as areused above may be used as the term, “static PLS signaling data” thatmeans that remains static for the duration of a frame or a group offrames. And the terms “dynamic L1-post signaling” may be called as theterms, “dynamic PLS signaling data” that may dynamically changeframe-by-frame.

And, the above-used terms, “signaling information” and the terms, “AP1signaling information” may correspond to a preamble part that will beexplained hereinafter.

Accordingly, for example, the terms, “L1_MOD field” may also be a pieceof information on modulation of the PLS data.

FIG. 64 illustrates a flowchart showing a method for transmittingbroadcast data according to an embodiment of the present invention. Thisprocess is also disclosed in the embodiment of FIGS. 25 and 27 and willbe described in FIG. 67 as well.

The broadcast service data carried in a transmission unit such as a PLPor DP may be processed and transmitted through an input processor, aBICM module, a frame builder, and an OFDM generator as FIGS. 6 and 66disclose. In details, the process is described below.

First, as an example, the embodiments of the input processor aredescribed in FIGS. 4 to 6, or FIGS. 67 and 69.

Herein, input data are processed to output transmission unit data(S4400000). The input data may have various formats. For example theinput data may be MPEG-2 transport streams, or IP streams.

The transmission unit data are encoded by an encoding scheme (S4400100).For example, as one encoding method, LDCP encoding may be used in thisprocess. When the LDPC encoding is used for the FEC, a set ofLPDC-encoded bits of the transmission unit data may be output by thisprocess. This process may be performed in the embodiment of FIG. 17 andwill be described in FIG. 70.

The encoded transmission unit data are interleaved (S4400200). Theinterleaving may be operated at the bit-level.

The interleaved transmission unit data are mapped (S4400300). In thisprocess, one of variety of symbol-mapping methods may be used. When thetransmission unit data are mapped onto constellations, the cell which ismodulation value that is carried by one carrier of the OFDM transmissionare outputted.

Even though this figure does not disclose, the interleaved transmissionunit data may be de-multiplexed in accordance with a symbol-mappingmethod and/or a code rate in order to enhance the performance of the FECencoding. At this time, the order of the bit-interleaved service datamay be different from the order of the bits to be mapped in accordancewith a symbol-mapping method and/or a code rate.

And, the mapped service data are MIMO-encoded using a MIMO matrix. Upontransmitting broadcast signals including the transmission unit datathrough a plurality of antennas, several types of MIMO encodings may beapplied to the transmission data in this stage.

Signal frames including the mapped transmission unit data are built(S4400400).

As described, the signaling data (L1 signaling information) may includetwo parts. The first part carries basic information about the system aswell as the parameters needed to decode the second part. The second partcarries more detailed signaling data about the transmission system andthe PLPs or DPs. FIGS. 44 to 47 disclose about the detailed informationfor the signaling data.

For example, the signaling data includes MIMO encoding informationrelated to the transmission unit data as described in FIG. 47.

The signal frames are modulated by OFDM (Orthogonal Frequency DivisionMultiplex) scheme (S4400500).

This process may be performed in the embodiment of FIG. 19 or will bedescribed in FIG. 72.

The modulated signal frames are transmitted in a single frequency(S4400600). The signal frames processed by the above process aretransmitted as FIGS. 1 to 5 or FIG. 82 are described.

The structure of signal frame which is transmitted by the above processis described with reference to FIG. 82.

For example, the modulated signal frames are multiplexed in a superframe. The modulated signal frames includes a signal frame for mobilereception and a signal frame for fixed reception.

The signaling data includes a pilot pattern of the corresponding signalframe.

The signal frame may include a preamble having a guard interval, whichis generated by combining a cyclic prefix of an OFDM symbol of thepreamble and a specific sequence. And, as the specific sequence, Binarychirp-like sequence may be used.

The detailed embodiment for generating the preamble is described below.

FIG. 65 illustrates a flowchart showing a method for receiving broadcastdata according to an embodiment of the present invention. The embodimentof receiving the broadcast data may be compatible with the embodimentsin FIGS. 27 to 37, and may be described in FIGS. 73 to 80 as well.

When a receiver receives the broadcast signals which are transmitted bythe above processes, the broadcast signals are tuned and thendemodulated using an Orthogonal Frequency Division Multiplexing (OFDM)method (S4400800). At the time of receiving the signals, the receivermay use multiple antennas.

The signaling data at the beginning of a signal frame are decoded(S4400900).

FIGS. 44 to 47 disclose about the detailed information for the signalingdata. For example, the modulated signal frames have different frametypes in time domain, the different frame types of signal frames aremultiplexed in a super frame, which is a set of the signal frames. Then,the signaling data may have information on the different frame types ofsignal frame.

As another example, the signal data may include information on the MIMOencoding, which is applied to associated transmission unit data.

The signal frame including transmission unit data is parsed based on thedecoded signal data (S4401000).

And, The transmission unit data are demapped (S4401100).

The demapped transmission unit data are de-interleaved (S4401200).

The de-interleaved transmission unit data are decoded (S4401300). Forexample, the transmission unit data are FEC-decoded based on a LDPCencoding method and the receiver can detect the code rate and FEC-typeinformation in the signaling data which is described in FIGS. 44 to 47.

The decoded transmission unit data are processed to output service data(S4401400). This process is described with reference to FIGS. 33, 34 and77.

The present invention provides apparatuses and methods for transmittingand receiving broadcast signals for future broadcast services. Futurebroadcast services according to an embodiment of the present inventioninclude a terrestrial broadcast service, a mobile broadcast service, aUHDTV service, etc. The present invention may process broadcast signalsfor the future broadcast services through non-MIMO (Multiple InputMultiple Output) or MIMO according to one embodiment. A non-MIMO schemeaccording to an embodiment of the present invention may include a MISO(Multiple Input Single Output) scheme, a SISO (Single Input SingleOutput) scheme, etc.

While MISO or MIMO uses two antennas in the following for convenience ofdescription, the present invention is applicable to systems using two ormore antennas.

FIG. 66 illustrates a structure of an apparatus for transmittingbroadcast signals for future broadcast services according to anembodiment of the present invention.

The apparatus for transmitting broadcast signals for future broadcastservices according to an embodiment of the present invention can includean input formatting module 1000, a coding & modulation module 1100, aframe structure module 1200, a waveform generation module 1300 and asignaling generation module 1400. A description will be given of theoperation of each module of the apparatus for transmitting broadcastsignals.

Referring to FIG. 66, the apparatus for transmitting broadcast signalsfor future broadcast services according to an embodiment of the presentinvention can receive MPEG-TSs, IP streams (v4/v6) and generic streams(GSs) as an input signal. In addition, the apparatus for transmittingbroadcast signals can receive management information about theconfiguration of each stream constituting the input signal and generatea final physical layer signal with reference to the received managementinformation.

The input formatting module 1000 according to an embodiment of thepresent invention can classify the input streams on the basis of astandard for coding and modulation or services or service components andoutput the input streams as a plurality of logical data pipes (or datapipes or DP data). The data pipe is a logical channel in the physicallayer that carries service data or related metadata, which may carry oneor multiple service(s) or service component(s). In addition, datatransmitted through each data pipe may be called DP data.

In addition, the input formatting module 1000 according to an embodimentof the present invention can divide each data pipe into blocks necessaryto perform coding and modulation and carry out processes necessary toincrease transmission efficiency or to perform scheduling. Details ofoperations of the input formatting module 1000 will be described later.

The coding & modulation module 1100 according to an embodiment of thepresent invention can perform forward error correction (FEC) encoding oneach data pipe received from the input formatting module 1000 such thatan apparatus for receiving broadcast signals can correct an error thatmay be generated on a transmission channel. In addition, the coding &modulation module 1100 according to an embodiment of the presentinvention can convert FEC output bit data to symbol data and interleavethe symbol data to correct burst error caused by a channel. As shown inFIG. 66, the coding & modulation module 1100 according to an embodimentof the present invention can divide the processed data such that thedivided data can be output through data paths for respective antennaoutputs in order to transmit the data through two or more Tx antennas.

The frame structure module 1200 according to an embodiment of thepresent invention can map the data output from the coding & modulationmodule 1100 to signal frames. The frame structure module 1200 accordingto an embodiment of the present invention can perform mapping usingscheduling information output from the input formatting module 1000 andinterleave data in the signal frames in order to obtain additionaldiversity gain.

The waveform generation module 1300 according to an embodiment of thepresent invention can convert the signal frames output from the framestructure module 1200 into a signal for transmission. In this case, thewaveform generation module 1300 according to an embodiment of thepresent invention can insert a preamble signal (or preamble) into thesignal for detection of the transmission apparatus and insert areference signal for estimating a transmission channel to compensate fordistortion into the signal. In addition, the waveform generation module1300 according to an embodiment of the present invention can provide aguard interval and insert a specific sequence into the same in order tooffset the influence of channel delay spread due to multi-pathreception. Additionally, the waveform generation module 1300 accordingto an embodiment of the present invention can perform a procedurenecessary for efficient transmission in consideration of signalcharacteristics such as a peak-to-average power ratio of the outputsignal.

The signaling generation module 1400 according to an embodiment of thepresent invention generates final physical layer signaling informationusing the input management information and information generated by theinput formatting module 1000, coding & modulation module 1100 and framestructure module 1200. Accordingly, a reception apparatus according toan embodiment of the present invention can decode a received signal bydecoding the signaling information.

As described above, the apparatus for transmitting broadcast signals forfuture broadcast services according to one embodiment of the presentinvention can provide terrestrial broadcast service, mobile broadcastservice, UHDTV service, etc. Accordingly, the apparatus for transmittingbroadcast signals for future broadcast services according to oneembodiment of the present invention can multiplex signals for differentservices in the time domain and transmit the same.

FIGS. 67, 68 and 69 illustrate the input formatting module 1000according to embodiments of the present invention. A description will begiven of each figure.

FIG. 67 illustrates an input formatting module according to oneembodiment of the present invention. FIG. 67 shows an input formattingmodule when the input signal is a single input stream.

Referring to FIG. 67, the input formatting module according to oneembodiment of the present invention can include a mode adaptation module2000 and a stream adaptation module 2100.

As shown in FIG. 67, the mode adaptation module 2000 can include aninput interface block 2010, a CRC-8 encoder block 2020 and a BB headerinsertion block 2030. Description will be given of each block of themode adaptation module 2000.

The input interface block 2010 can divide the single input stream inputthereto into data pieces each having the length of a baseband (BB) frameused for FEC (BCH/LDPC) which will be performed later and output thedata pieces.

The CRC-8 encoder block 2020 can perform CRC encoding on BB frame datato add redundancy data thereto.

The BB header insertion block 2030 can insert, into the BB frame data, aheader including information such as mode adaptation type (TS/GS/IP), auser packet length, a data field length, user packet sync byte, startaddress of user packet sync byte in data field, a high efficiency modeindicator, an input stream synchronization field, etc.

As shown in FIG. 67, the stream adaptation module 2100 can include apadding insertion block 2110 and a BB scrambler block 2120. Descriptionwill be given of each block of the stream adaptation module 2100.

If data received from the mode adaptation module 2000 has a lengthshorter than an input data length necessary for FEC encoding, thepadding insertion block 2110 can insert a padding bit into the data suchthat the data has the input data length and output the data includingthe padding bit.

The BB scrambler block 2120 can randomize the input bit stream byperforming an XOR operation on the input bit stream and a pseudo randombinary sequence (PRBS).

The above-described blocks may be omitted or replaced by blocks havingsimilar or identical functions.

As shown in FIG. 67, the input formatting module can finally output datapipes to the coding & modulation module.

FIG. 68 illustrates an input formatting module according to anotherembodiment of the present invention. FIG. 68 shows a mode adaptationmodule 3000 of the input formatting module when the input signalcorresponds to multiple input streams.

The mode adaptation module 3000 of the input formatting module forprocessing the multiple input streams can independently process themultiple input streams.

Referring to FIG. 68, the mode adaptation module 3000 for respectivelyprocessing the multiple input streams can include input interfaceblocks, input stream synchronizer blocks 3100, compensating delay blocks3200, null packet deletion blocks 3300, CRC-8 encoder blocks and BBheader insertion blocks. Description will be given of each block of themode adaptation module 3000.

Operations of the input interface block, CRC-8 encoder block and BBheader insertion block correspond to those of the input interface block,CRC-8 encoder block and BB header insertion block described withreference to FIG. 67 and thus description thereof is omitted.

The input stream synchronizer block 3100 can transmit input stream clockreference (ISCR) information to generate timing information necessaryfor the apparatus for receiving broadcast signals to restore the TSs orGSs.

The compensating delay block 3200 can delay input data and output thedelayed input data such that the apparatus for receiving broadcastsignals can synchronize the input data if a delay is generated betweendata pipes according to processing of data including the timinginformation by the transmission apparatus.

The null packet deletion block 3300 can delete unnecessarily transmittedinput null packets from the input data, insert the number of deletednull packets into the input data based on positions in which the nullpackets are deleted and transmit the input data.

The above-described blocks may be omitted or replaced by blocks havingsimilar or identical functions.

FIG. 69 illustrates an input formatting module according to anotherembodiment of the present invention.

Specifically, FIG. 69 illustrates a stream adaptation module of theinput formatting module when the input signal corresponds to multipleinput streams.

The stream adaptation module of the input formatting module when theinput signal corresponds to multiple input streams can include ascheduler 4000, a 1-frame delay block 4100, an in-band signaling orpadding insertion block 4200, a physical layer signaling generationblock 4300 and a BB scrambler block 4400. Description will be given ofeach block of the stream adaptation module.

The scheduler 4000 can perform scheduling for a MIMO system usingmultiple antennas having dual polarity. In addition, the scheduler 4000can generate parameters for use in signal processing blocks for antennapaths, such as a bit-to-cell demux block, a cell interleaver block, atime interleaver block, etc. included in the coding & modulation moduleillustrated in FIG. 66.

The 1-frame delay block 4100 can delay the input data by onetransmission frame such that scheduling information about the next framecan be transmitted through the current frame for in-band signalinginformation to be inserted into the data pipes.

The in-band signaling or padding insertion block 4200 can insertundelayed physical layer signaling (PLS)-dynamic signaling informationinto the data delayed by one transmission frame. In this case, thein-band signaling or padding insertion block 4200 can insert a paddingbit when a space for padding is present or insert in-band signalinginformation into the padding space. In addition, the scheduler 4000 canoutput physical layer signaling-dynamic signaling information about thecurrent frame separately from in-band signaling information.Accordingly, a cell mapper, which will be described later, can map inputcells according to scheduling information output from the scheduler4000.

The physical layer signaling generation block 4300 can generate physicallayer signaling data which will be transmitted through a preamble symbolof a transmission frame or spread and transmitted through a data symbolother than the in-band signaling information. In this case, the physicallayer signaling data according to an embodiment of the present inventioncan be referred to as signaling information. Furthermore, the physicallayer signaling data according to an embodiment of the present inventioncan be divided into PLS-pre information and PLS-post information. ThePLS-pre information can include parameters necessary to encode thePLS-post information and static PLS signaling data and the PLS-postinformation can include parameters necessary to encode the data pipes.The parameters necessary to encode the data pipes can be classified intostatic PLS signaling data and dynamic PLS signaling data. The static PLSsignaling data is a parameter commonly applicable to all frames includedin a super-frame and can be changed on a super-frame basis. The dynamicPLS signaling data is a parameter differently applicable to respectiveframes included in a super-frame and can be changed on a frame-by-framebasis. Accordingly, the reception apparatus can acquire the PLS-postinformation by decoding the PLS-pre information and decode desired datapipes by decoding the PLS-post information.

The BB scrambler block 4400 can generate a pseudo-random binary sequence(PRBS) and perform an XOR operation on the PRBS and the input bitstreams to decrease the peak-to-average power ratio (PAPR) of the outputsignal of the waveform generation block. As shown in FIG. 69, scramblingof the BB scrambler block 4400 is applicable to both data pipes andphysical layer signaling information.

The above-described blocks may be omitted or replaced by blocks havingsimilar or identical functions according to designer.

As shown in FIG. 69, the stream adaptation module can finally output thedata pipes to the coding & modulation module.

FIG. 70 illustrates a coding & modulation module according to anembodiment of the present invention.

The coding & modulation module shown in FIG. 70 corresponds to anembodiment of the coding & modulation module illustrated in FIG. 66.

As described above, the apparatus for transmitting broadcast signals forfuture broadcast services according to an embodiment of the presentinvention can provide a terrestrial broadcast service, mobile broadcastservice, UHDTV service, etc.

Since QoS (quality of service) depends on characteristics of a serviceprovided by the apparatus for transmitting broadcast signals for futurebroadcast services according to an embodiment of the present invention,data corresponding to respective services needs to be processed throughdifferent schemes. Accordingly, the coding & modulation module accordingto an embodiment of the present invention can independently process datapipes input thereto by independently applying SISO, MISO and MIMOschemes to the data pipes respectively corresponding to data paths.Consequently, the apparatus for transmitting broadcast signals forfuture broadcast services according to an embodiment of the presentinvention can control QoS for each service or service componenttransmitted through each data pipe.

Accordingly, the coding & modulation module according to an embodimentof the present invention can include a first block 5000 for SISO, asecond block 5100 for MISO, a third block 5200 for MIMO and a fourthblock 5300 for processing the PLS-pre/PLS-post information. The coding &modulation module illustrated in FIG. 70 is an exemplary and may includeonly the first block 5000 and the fourth block 5300, the second block5100 and the fourth block 5300 or the third block 5200 and the fourthblock 5300 according to design. That is, the coding & modulation modulecan include blocks for processing data pipes equally or differentlyaccording to design.

A description will be given of each block of the coding & modulationmodule.

The first block 5000 processes an input data pipe according to SISO andcan include an FEC encoder block 5010, a bit interleaver block 5020, abit-to-cell demux block 5030, a constellation mapper block 5040, a cellinterleaver block 5050 and a time interleaver block 5060.

The FEC encoder block 5010 can perform BCH encoding and LDPC encoding onthe input data pipe to add redundancy thereto such that the receptionapparatus can correct an error generated on a transmission channel.

The bit interleaver block 5020 can interleave bit streams of theFEC-encoded data pipe according to an interleaving rule such that thebit streams have robustness against burst error that may be generated onthe transmission channel. Accordingly, when deep fading or erasure isapplied to QAM symbols, errors can be prevented from being generated inconsecutive bits from among all codeword bits since interleaved bits aremapped to the QAM symbols.

The bit-to-cell demux block 5030 can determine the order of input bitstreams such that each bit in an FEC block can be transmitted withappropriate robustness in consideration of both the order of input bitstreams and a constellation mapping rule.

In addition, the bit interleaver block 5020 is located between the FECencoder block 5010 and the constellation mapper block 5040 and canconnect output bits of LDPC encoding performed by the FEC encoder block5010 to bit positions having different reliability values and optimalvalues of the constellation mapper in consideration of LDPC decoding ofthe apparatus for receiving broadcast signals. Accordingly, thebit-to-cell demux block 5030 can be replaced by a block having a similaror equal function.

The constellation mapper block 5040 can map a bit word input thereto toone constellation. In this case, the constellation mapper block 5040 canadditionally perform rotation & Q-delay. That is, the constellationmapper block 5040 can rotate input constellations according to arotation angle, divide the constellations into an in-phase component anda quadrature-phase component and delay only the quadrature-phasecomponent by an arbitrary value. Then, the constellation mapper block5040 can remap the constellations to new constellations using a pairedin-phase component and quadrature-phase component.

In addition, the constellation mapper block 5040 can move constellationpoints on a two-dimensional plane in order to find optimal constellationpoints. Through this process, capacity of the coding & modulation module1100 can be optimized. Furthermore, the constellation mapper block 5040can perform the above-described operation using IQ-balancedconstellation points and rotation. The constellation mapper block 5040can be replaced by a block having a similar or equal function.

The cell interleaver block 5050 can randomly interleave cellscorresponding to one FEC block and output the interleaved cells suchthat cells corresponding to respective FEC blocks can be output indifferent orders.

The time interleaver block 5060 can interleave cells belonging to aplurality of FEC blocks and output the interleaved cells. Accordingly,the cells corresponding to the FEC blocks are dispersed and transmittedin a period corresponding to a time interleaving depth and thusdiversity gain can be obtained.

The second block 5100 processes an input data pipe according to MISO andcan include the FEC encoder block, bit interleaver block, bit-to-celldemux block, constellation mapper block, cell interleaver block and timeinterleaver block in the same manner as the first block 5000. However,the second block 5100 is distinguished from the first block 5000 in thatthe second block 5100 further includes a MISO processing block 5110. Thesecond block 5100 performs the same procedure including the inputoperation to the time interleaver operation as those of the first block5000 and thus description of the corresponding blocks is omitted.

The MISO processing block 5110 can encode input cells according to aMISO encoding matrix providing transmit diversity and outputMISO-processed data through two paths. MISO processing according to oneembodiment of the present invention can include OSTBC (orthogonal spacetime block coding)/OSFBC (orthogonal space frequency block coding,Alamouti coding).

The third block 5200 processes an input data pipe according to MIMO andcan include the FEC encoder block, bit interleaver block, bit-to-celldemux block, constellation mapper block, cell interleaver block and timeinterleaver block in the same manner as the second block 5100, as shownin FIG. 70. However, the data processing procedure of the third block5200 is different from that of the second block 5100 since the thirdblock 5200 includes a MIMO processing block 5220.

That is, in the third block 5200, basic roles of the FEC encoder blockand the bit interleaver block are identical to those of the first andsecond blocks 5000 and 5100 although functions thereof may be differentfrom those of the first and second blocks 5000 and 5100.

The bit-to-cell demux block 5210 can generate as many output bit streamsas input bit streams of MIMO processing and output the output bitstreams through MIMO paths for MIMO processing. In this case, thebit-to-cell demux block 5210 can be designed to optimize the decodingperformance of the reception apparatus in consideration ofcharacteristics of LDPC and MIMO processing.

Basic roles of the constellation mapper block, cell interleaver blockand time interleaver block are identical to those of the first andsecond blocks 5000 and 5100 although functions thereof may be differentfrom those of the first and second blocks 5000 and 5100. As shown inFIG. 70, as many constellation mapper blocks, cell interleaver blocksand time interleaver blocks as the number of MIMO paths for MIMOprocessing can be present. In this case, the constellation mapperblocks, cell interleaver blocks and time interleaver blocks can operateequally or independently for data input through the respective paths.

The MIMO processing block 5220 can perform MIMO processing on two inputcells using a MIMO encoding matrix and output the MIMO-processed datathrough two paths. The MIMO encoding matrix according to an embodimentof the present invention can include spatial multiplexing, Golden code,full-rate full diversity code, linear dispersion code, etc.

The fourth block 5300 processes the PLS-pre/PLS-post information and canperform SISO or MISO processing.

The basic roles of the bit interleaver block, bit-to-cell demux block,constellation mapper block, cell interleaver block, time interleaverblock and MISO processing block included in the fourth block 5300correspond to those of the second block 5100 although functions thereofmay be different from those of the second block 5100.

A shortened/punctured FEC encoder block 5310 included in the fourthblock 5300 can process PLS data using an FEC encoding scheme for a PLSpath provided for a case in which the length of input data is shorterthan a length necessary to perform FEC encoding. Specifically, theshortened/punctured FEC encoder block 5310 can perform BCH encoding oninput bit streams, pad 0s corresponding to a desired input bit streamlength necessary for normal LDPC encoding, carry out LDPC encoding andthen remove the padded 0s to puncture parity bits such that an effectivecode rate becomes equal to or lower than the data pipe rate.

The blocks included in the first block 5000 to fourth block 5300 may beomitted or replaced by blocks having similar or identical functionsaccording to design.

As illustrated in FIG. 70, the coding & modulation module can output thedata pipes (or DP data), PLS-pre information and PLS-post informationprocessed for the respective paths to the frame structure module.

FIG. 71 illustrates a frame structure module according to one embodimentof the present invention.

The frame structure module shown in FIG. 71 corresponds to an embodimentof the frame structure module 1200 illustrated in FIG. 66.

The frame structure module according to one embodiment of the presentinvention can include at least one cell-mapper 6000, at least one delaycompensation module 6100 and at least one block interleaver 6200. Thenumber of cell mappers 6000, delay compensation modules 6100 and blockinterleavers 6200 can be changed. A description will be given of eachmodule of the frame structure block.

The cell-mapper 6000 can allocate cells corresponding to SISO-, MISO- orMIMO-processed data pipes output from the coding & modulation module,cells corresponding to common data commonly applicable to the data pipesand cells corresponding to the PLS-pre/PLS-post information to signalframes according to scheduling information. The common data refers tosignaling information commonly applied to all or some data pipes and canbe transmitted through a specific data pipe. The data pipe through whichthe common data is transmitted can be referred to as a common data pipeand can be changed according to design.

When the apparatus for transmitting broadcast signals according to anembodiment of the present invention uses two output antennas andAlamouti coding is used for MISO processing, the cell-mapper 6000 canperform pair-wise cell mapping in order to maintain orthogonalityaccording to Alamouti encoding. That is, the cell-mapper 6000 canprocess two consecutive cells of the input cells as one unit and map theunit to a frame. Accordingly, paired cells in an input pathcorresponding to an output path of each antenna can be allocated toneighboring positions in a transmission frame.

The delay compensation block 6100 can obtain PLS data corresponding tothe current transmission frame by delaying input PLS data cells for thenext transmission frame by one frame. In this case, the PLS datacorresponding to the current frame can be transmitted through a preamblepart in the current signal frame and PLS data corresponding to the nextsignal frame can be transmitted through a preamble part in the currentsignal frame or in-band signaling in each data pipe of the currentsignal frame. This can be changed by the designer.

The block interleaver 6200 can obtain additional diversity gain byinterleaving cells in a transport block corresponding to the unit of asignal frame. In addition, the block interleaver 6200 can performinterleaving by processing two consecutive cells of the input cells asone unit when the above-described pair-wise cell mapping is performed.Accordingly, cells output from the block interleaver 6200 can be twoconsecutive identical cells.

When pair-wise mapping and pair-wise interleaving are performed, atleast one cell mapper and at least one block interleaver can operateequally or independently for data input through the paths.

The above-described blocks may be omitted or replaced by blocks havingsimilar or identical functions according to design.

As illustrated in FIG. 71, the frame structure module can output atleast one signal frame to the waveform generation module.

FIG. 72 illustrates a waveform generation module according to anembodiment of the present invention.

The waveform generation module illustrated in FIG. 72 corresponds to anembodiment of the waveform generation module 1300 described withreference to FIG. 66.

The waveform generation module according to an embodiment of the presentinvention can modulate and transmit as many signal frames as the numberof antennas for receiving and outputting signal frames output from theframe structure module illustrated in FIG. 71.

Specifically, the waveform generation module illustrated in FIG. 72 isan embodiment of a waveform generation module of an apparatus fortransmitting broadcast signals using m Tx antennas and can include mprocessing blocks for modulating and outputting frames corresponding tom paths. The m processing blocks can perform the same processingprocedure. A description will be given of operation of the firstprocessing block 7000 from among the m processing blocks.

The first processing block 7000 can include a reference signal & PAPRreduction block 7100, an inverse waveform transform block 7200, a PAPRreduction in time block 7300, a guard sequence insertion block 7400, apreamble insertion block 7500, a waveform processing block 7600, othersystem insertion block 7700 and a DAC (digital analog converter) block7800.

The reference signal insertion & PAPR reduction block 7100 can insert areference signal into a predetermined position of each signal block andapply a PAPR reduction scheme to reduce a PAPR in the time domain. If abroadcast transmission/reception system according to an embodiment ofthe present invention corresponds to an OFDM system, the referencesignal insertion & PAPR reduction block 7100 can use a method ofreserving some active subcarriers rather than using the same. Inaddition, the reference signal insertion & PAPR reduction block 7100 maynot use the PAPR reduction scheme as an optional feature according tobroadcast transmission/reception system.

The inverse waveform transform block 7200 can transform an input signalin a manner of improving transmission efficiency and flexibility inconsideration of transmission channel characteristics and systemarchitecture. If the broadcast transmission/reception system accordingto an embodiment of the present invention corresponds to an OFDM system,the inverse waveform transform block 7200 can employ a method oftransforming a frequency domain signal into a time domain signal throughinverse FFT operation. If the broadcast transmission/reception systemaccording to an embodiment of the present invention corresponds to asingle carrier system, the inverse waveform transform block 7200 may notbe used in the waveform generation module.

The PAPR reduction in time block 7300 can use a method for reducing PAPRof an input signal in the time domain. If the broadcasttransmission/reception system according to an embodiment of the presentinvention corresponds to an OFDM system, the PAPR reduction in timeblock 7300 may use a method of simply clipping peak amplitude.Furthermore, the PAPR reduction in time block 7300 may not be used inthe broadcast transmission/reception system according to an embodimentof the present invention since it is an optional feature.

The guard sequence insertion block 7400 can provide a guard intervalbetween neighboring signal blocks and insert a specific sequence intothe guard interval as necessary in order to minimize the influence ofdelay spread of a transmission channel. Accordingly, the receptionapparatus can easily perform synchronization or channel estimation. Ifthe broadcast transmission/reception system according to an embodimentof the present invention corresponds to an OFDM system, the guardsequence insertion block 7400 may insert a cyclic prefix into a guardinterval of an OFDM symbol.

The preamble insertion block 7500 can insert a signal of a known type(e.g. the preamble or preamble symbol) agreed upon between thetransmission apparatus and the reception apparatus into a transmissionsignal such that the reception apparatus can rapidly and efficientlydetect a target system signal. If the broadcast transmission/receptionsystem according to an embodiment of the present invention correspondsto an OFDM system, the preamble insertion block 7500 can define a signalframe composed of a plurality of OFDM symbols and insert a preamblesymbol into the beginning of each signal frame. That is, the preamblecarries basic PLS data and is located in the beginning of a signalframe.

The waveform processing block 7600 can perform waveform processing on aninput baseband signal such that the input baseband signal meets channeltransmission characteristics. The waveform processing block 7600 may usea method of performing square-root-raised cosine (SRRC) filtering toobtain a standard for out-of-band emission of a transmission signal. Ifthe broadcast transmission/reception system according to an embodimentof the present invention corresponds to a multi-carrier system, thewaveform processing block 7600 may not be used.

The other system insertion block 7700 can multiplex signals of aplurality of broadcast transmission/reception systems in the time domainsuch that data of two or more different broadcast transmission/receptionsystems providing broadcast services can be simultaneously transmittedin the same RF signal bandwidth. In this case, the two or more differentbroadcast transmission/reception systems refer to systems providingdifferent broadcast services. The different broadcast services may referto a terrestrial broadcast service, mobile broadcast service, etc. Datarelated to respective broadcast services can be transmitted throughdifferent frames.

The DAC block 7800 can convert an input digital signal into an analogsignal and output the analog signal. The signal output from the DACblock 7800 can be transmitted through m output antennas. A Tx antennaaccording to an embodiment of the present invention can have vertical orhorizontal polarity.

The above-described blocks may be omitted or replaced by blocks havingsimilar or identical functions according to design.

FIG. 73 illustrates a structure of an apparatus for receiving broadcastsignals for future broadcast services according to an embodiment of thepresent invention.

The apparatus for receiving broadcast signals for future broadcastservices according to an embodiment of the present invention cancorrespond to the apparatus for transmitting broadcast signals forfuture broadcast services, described with reference to FIG. 66. Theapparatus for receiving broadcast signals for future broadcast servicesaccording to an embodiment of the present invention can include asynchronization & demodulation module 8000, a frame parsing module 8100,a demapping & decoding module 8200, an output processor 8300 and asignaling decoding module 8400. A description will be given of operationof each module of the apparatus for receiving broadcast signals.

The synchronization & demodulation module 8000 can receive input signalsthrough m Rx antennas, perform signal detection and synchronization withrespect to a system corresponding to the apparatus for receivingbroadcast signals and carry out demodulation corresponding to a reverseprocedure of the procedure performed by the apparatus for transmittingbroadcast signals.

The frame parsing module 8100 can parse input signal frames and extractdata through which a service selected by a user is transmitted. If theapparatus for transmitting broadcast signals performs interleaving, theframe parsing module 8100 can carry out deinterleaving corresponding toa reverse procedure of interleaving. In this case, the positions of asignal and data that need to be extracted can be obtained by decodingdata output from the signaling decoding module 8400 to restorescheduling information generated by the apparatus for transmittingbroadcast signals.

The demapping & decoding module 8200 can convert the input signals intobit domain data and then deinterleave the same as necessary. Thedemapping & decoding module 8200 can perform demapping for mappingapplied for transmission efficiency and correct an error generated on atransmission channel through decoding. In this case, the demapping &decoding module 8200 can obtain transmission parameters necessary fordemapping and decoding by decoding the data output from the signalingdecoding module 8400.

The output processor 8300 can perform reverse procedures of variouscompression/signal processing procedures which are applied by theapparatus for transmitting broadcast signals to improve transmissionefficiency. In this case, the output processor 8300 can acquirenecessary control information from data output from the signalingdecoding module 8400. The output of the output processor 8300corresponds to a signal input to the apparatus for transmittingbroadcast signals and may be MPEG-TSs, IP streams (v4 or v6) and genericstreams.

The signaling decoding module 8400 can obtain PLS information from thesignal demodulated by the synchronization & demodulation module 8000. Asdescribed above, the frame parsing module 8100, demapping & decodingmodule 8200 and output processor 8300 can execute functions thereofusing the data output from the signaling decoding module 8400.

FIG. 74 illustrates a synchronization & demodulation module according toan embodiment of the present invention.

The synchronization & demodulation module shown in FIG. 74 correspondsto an embodiment of the synchronization & demodulation module describedwith reference to FIG. 73. The synchronization & demodulation moduleshown in FIG. 74 can perform a reverse operation of the operation of thewaveform generation module illustrated in FIG. 72.

As shown in FIG. 74, the synchronization & demodulation module accordingto an embodiment of the present invention corresponds to asynchronization & demodulation module of an apparatus for receivingbroadcast signals using m Rx antennas and can include m processingblocks for demodulating signals respectively input through m paths. Them processing blocks can perform the same processing procedure. Adescription will be given of operation of the first processing block9000 from among the m processing blocks.

The first processing block 9000 can include a tuner 9100, an ADC block9200, a preamble detector 9300, a guard sequence detector 9400, awaveform transform block 9500, a time/frequency synchronization block9600, a reference signal detector 9700, a channel equalizer 9800 and aninverse waveform transform block 9900.

The tuner 9100 can select a desired frequency band, compensate for themagnitude of a received signal and output the compensated signal to theADC block 9200.

The ADC block 9200 can convert the signal output from the tuner 9100into a digital signal.

The preamble detector 9300 can detect a preamble (or preamble signal orpreamble symbol) in order to check whether or not the digital signal isa signal of the system corresponding to the apparatus for receivingbroadcast signals. In this case, the preamble detector 9300 can decodebasic transmission parameters received through the preamble.

The guard sequence detector 9400 can detect a guard sequence in thedigital signal. The time/frequency synchronization block 9600 canperform time/frequency synchronization using the detected guard sequenceand the channel equalizer 9800 can estimate a channel through areceived/restored sequence using the detected guard sequence.

The waveform transform block 9500 can perform a reverse operation ofinverse waveform transform when the apparatus for transmitting broadcastsignals has performed inverse waveform transform. When the broadcasttransmission/reception system according to one embodiment of the presentinvention is a multi-carrier system, the waveform transform block 9500can perform FFT. Furthermore, when the broadcast transmission/receptionsystem according to an embodiment of the present invention is a singlecarrier system, the waveform transform block 9500 may not be used if areceived time domain signal is processed in the frequency domain orprocessed in the time domain.

The time/frequency synchronization block 9600 can receive output data ofthe preamble detector 9300, guard sequence detector 9400 and referencesignal detector 9700 and perform time synchronization and carrierfrequency synchronization including guard sequence detection and blockwindow positioning on a detected signal. Here, the time/frequencysynchronization block 9600 can feed back the output signal of thewaveform transform block 9500 for frequency synchronization.

The reference signal detector 9700 can detect a received referencesignal. Accordingly, the apparatus for receiving broadcast signalsaccording to an embodiment of the present invention can performsynchronization or channel estimation.

The channel equalizer 9800 can estimate a transmission channel from eachTx antenna to each Rx antenna from the guard sequence or referencesignal and perform channel equalization for received data using theestimated channel.

The inverse waveform transform block 9900 may restore the originalreceived data domain when the waveform transform block 9500 performswaveform transform for efficient synchronization and channelestimation/equalization. If the broadcast transmission/reception systemaccording to an embodiment of the present invention is a single carriersystem, the waveform transform block 9500 can perform FFT in order tocarry out synchronization/channel estimation/equalization in thefrequency domain and the inverse waveform transform block 9900 canperform IFFT on the channel-equalized signal to restore transmitted datasymbols. If the broadcast transmission/reception system according to anembodiment of the present invention is a multi-carrier system, theinverse waveform transform block 9900 may not be used.

The above-described blocks may be omitted or replaced by blocks havingsimilar or identical functions according to design.

FIG. 75 illustrates a frame parsing module according to an embodiment ofthe present invention.

The frame parsing module illustrated in FIG. 75 corresponds to anembodiment of the frame parsing module described with reference to FIG.73. The frame parsing module shown in FIG. 75 can perform a reverseoperation of the operation of the frame structure module illustrated inFIG. 71.

As shown in FIG. 75, the frame parsing module according to an embodimentof the present invention can include at least one block interleaver10000 and at least one cell demapper 10100.

The block interleaver 10000 can deinterleave data input through datapaths of the m Rx antennas and processed by the synchronization &demodulation module on a signal block basis. In this case, if theapparatus for transmitting broadcast signals performs pair-wiseinterleaving as illustrated in FIG. 73, the block interleaver 10000 canprocess two consecutive pieces of data as a pair for each input path.Accordingly, the block interleaver 10000 can output two consecutivepieces of data even when deinterleaving has been performed. Furthermore,the block interleaver 10000 can perform a reverse operation of theinterleaving operation performed by the apparatus for transmittingbroadcast signals to output data in the original order.

The cell demapper 10100 can extract cells corresponding to common data,cells corresponding to data pipes and cells corresponding to PLS datafrom received signal frames. The cell demapper 10100 can merge datadistributed and transmitted and output the same as a stream asnecessary. When two consecutive pieces of cell input data are processedas a pair and mapped in the apparatus for transmitting broadcastsignals, as shown in FIG. 71, the cell demapper 10100 can performpair-wise cell demapping for processing two consecutive input cells asone unit as a reverse procedure of the mapping operation of theapparatus for transmitting broadcast signals.

In addition, the cell demapper 10100 can extract PLS signaling datareceived through the current frame as PLS-pre & PLS-post data and outputthe PLS-pre & PLS-post data.

The above-described blocks may be omitted or replaced by blocks havingsimilar or identical functions according to design.

FIG. 76 illustrates a demapping & decoding module according to anembodiment of the present invention.

The demapping & decoding module shown in FIG. 76 corresponds to anembodiment of the demapping & decoding module illustrated in FIG. 73.The demapping & decoding module shown in FIG. 76 can perform a reverseoperation of the operation of the coding & modulation module illustratedin FIG. 70.

The coding & modulation module of the apparatus for transmittingbroadcast signals according to an embodiment of the present inventioncan process input data pipes by independently applying SISO, MISO andMIMO thereto for respective paths, as described above. Accordingly, thedemapping & decoding module illustrated in FIG. 76 can include blocksfor processing data output from the frame parsing module according toSISO, MISO and MIMO in response to the apparatus for transmittingbroadcast signals.

As shown in FIG. 76, the demapping & decoding module according to anembodiment of the present invention can include a first block 11000 forSISO, a second block 11100 for MISO, a third block 11200 for MIMO and afourth block 11300 for processing the PLS-pre/PLS-post information. Thedemapping & decoding module shown in FIG. 76 is exemplary and mayinclude only the first block 11000 and the fourth block 11300, only thesecond block 11100 and the fourth block 11300 or only the third block11200 and the fourth block 11300 according to design. That is, thedemapping & decoding module can include blocks for processing data pipesequally or differently according to design.

A description will be given of each block of the demapping & decodingmodule.

The first block 11000 processes an input data pipe according to SISO andcan include a time deinterleaver block 11010, a cell deinterleaver block11020, a constellation demapper block 11030, a cell-to-bit mux block11040, a bit deinterleaver block 11050 and an FEC decoder block 11060.

The time deinterleaver block 11010 can perform a reverse process of theprocess performed by the time interleaver block 5060 illustrated in FIG.70. That is, the time deinterleaver block 11010 can deinterleave inputsymbols interleaved in the time domain into original positions thereof.

The cell deinterleaver block 11020 can perform a reverse process of theprocess performed by the cell interleaver block 5050 illustrated in FIG.70. That is, the cell deinterleaver block 11020 can deinterleavepositions of cells spread in one FEC block into original positionsthereof.

The constellation demapper block 11030 can perform a reverse process ofthe process performed by the constellation mapper block 5040 illustratedin FIG. 70. That is, the constellation demapper block 11030 can demap asymbol domain input signal to bit domain data. In addition, theconstellation demapper block 11030 may perform hard decision and outputdecided bit data. Furthermore, the constellation demapper block 11030may output a log-likelihood ratio (LLR) of each bit, which correspondsto a soft decision value or probability value. If the apparatus fortransmitting broadcast signals applies a rotated constellation in orderto obtain additional diversity gain, the constellation demapper block11030 can perform 2-dimensional LLR demapping corresponding to therotated constellation. Here, the constellation demapper block 11030 cancalculate the LLR such that a delay applied by the apparatus fortransmitting broadcast signals to the I or Q component can becompensated.

The cell-to-bit mux block 11040 can perform a reverse process of theprocess performed by the bit-to-cell demux block 5030 illustrated inFIG. 70. That is, the cell-to-bit mux block 11040 can restore bit datamapped by the bit-to-cell demux block 5030 to the original bit streams.

The bit deinterleaver block 11050 can perform a reverse process of theprocess performed by the bit interleaver 5020 illustrated in FIG. 70.That is, the bit deinterleaver block 11050 can deinterleave the bitstreams output from the cell-to-bit mux block 11040 in the originalorder.

The FEC decoder block 11060 can perform a reverse process of the processperformed by the FEC encoder block 5010 illustrated in FIG. 70. That is,the FEC decoder block 11060 can correct an error generated on atransmission channel by performing LDPC decoding and BCH decoding.

The second block 11100 processes an input data pipe according to MISOand can include the time deinterleaver block, cell deinterleaver block,constellation demapper block, cell-to-bit mux block, bit deinterleaverblock and FEC decoder block in the same manner as the first block 11000,as shown in FIG. 76. However, the second block 11100 is distinguishedfrom the first block 11000 in that the second block 11100 furtherincludes a MISO decoding block 11110. The second block 11100 performsthe same procedure including time deinterleaving operation to outputtingoperation as the first block 11000 and thus description of thecorresponding blocks is omitted.

The MISO decoding block 11110 can perform a reverse operation of theoperation of the MISO processing block 5110 illustrated in FIG. 70. Ifthe broadcast transmission/reception system according to an embodimentof the present invention uses STBC, the MISO decoding block 11110 canperform Alamouti decoding.

The third block 11200 processes an input data pipe according to MIMO andcan include the time deinterleaver block, cell deinterleaver block,constellation demapper block, cell-to-bit mux block, bit deinterleaverblock and FEC decoder block in the same manner as the second block11100, as shown in FIG. 76. However, the third block 11200 isdistinguished from the second block 11100 in that the third block 11200further includes a MIMO decoding block 11210. The basic roles of thetime deinterleaver block, cell deinterleaver block, constellationdemapper block, cell-to-bit mux block and bit deinterleaver blockincluded in the third block 11200 are identical to those of thecorresponding blocks included in the first and second blocks 11000 and11100 although functions thereof may be different from the first andsecond blocks 11000 and 11100.

The MIMO decoding block 11210 can receive output data of the celldeinterleaver for input signals of the m Rx antennas and perform MIMOdecoding as a reverse operation of the operation of the MIMO processingblock 5220 illustrated in FIG. 70. The MIMO decoding block 11210 canperform maximum likelihood decoding to obtain optimal decodingperformance or carry out sphere decoding with reduced complexity.Otherwise, the MIMO decoding block 11210 can achieve improved decodingperformance by performing MMSE detection or carrying out iterativedecoding with MMSE detection.

The fourth block 11300 processes the PLS-pre/PLS-post information andcan perform SISO or MISO decoding. The fourth block 11300 can carry outa reverse process of the process performed by the fourth block 5300described with reference to FIG. 70.

The basic roles of the time deinterleaver block, cell deinterleaverblock, constellation demapper block, cell-to-bit mux block and bitdeinterleaver block included in the fourth block 11300 are identical tothose of the corresponding blocks of the first, second and third blocks11000, 11100 and 11200 although functions thereof may be different fromthe first, second and third blocks 11000, 11100 and 11200.

The shortened/punctured FEC decoder 11310 included in the fourth block11300 can perform a reverse process of the process performed by theshortened/punctured FEC encoder block 5310 described with reference toFIG. 70. That is, the shortened/punctured FEC decoder 11310 can performde-shortening and de-puncturing on data shortened/punctured according toPLS data length and then carry out FEC decoding thereon. In this case,the FEC decoder used for data pipes can also be used for PLS.Accordingly, additional FEC decoder hardware for the PLS only is notneeded and thus system design is simplified and efficient coding isachieved.

The above-described blocks may be omitted or replaced by blocks havingsimilar or identical functions according to design.

The demapping & decoding module according to an embodiment of thepresent invention can output data pipes and PLS information processedfor the respective paths to the output processor, as illustrated in FIG.76.

FIGS. 77 and 78 illustrate output processors according to embodiments ofthe present invention.

FIG. 77 illustrates an output processor according to an embodiment ofthe present invention. The output processor illustrated in FIG. 77corresponds to an embodiment of the output processor illustrated in FIG.73. The output processor illustrated in FIG. 77 receives a single datapipe output from the demapping & decoding module and outputs a singleoutput stream. The output processor can perform a reverse operation ofthe operation of the input formatting module illustrated in FIG. 67.

The output processor shown in FIG. 77 can include a BB scrambler block12000, a padding removal block 12100, a CRC-8 decoder block 12200 and aBB frame processor block 12300.

The BB scrambler block 12000 can descramble an input bit stream bygenerating the same PRBS as that used in the apparatus for transmittingbroadcast signals for the input bit stream and carrying out an XORoperation on the PRBS and the bit stream.

The padding removal block 12100 can remove padding bits inserted by theapparatus for transmitting broadcast signals as necessary.

The CRC-8 decoder block 12200 can check a block error by performing CRCdecoding on the bit stream received from the padding removal block12100.

The BB frame processor block 12300 can decode information transmittedthrough a BB frame header and restore MPEG-TSs, IP streams (v4 or v6) orgeneric streams using the decoded information.

The above-described blocks may be omitted or replaced by blocks havingsimilar or identical functions according to design.

FIG. 78 illustrates an output processor according to another embodimentof the present invention. The output processor shown in FIG. 78corresponds to an embodiment of the output processor illustrated in FIG.73. The output processor shown in FIG. 78 receives multiple data pipesoutput from the demapping & decoding module. Decoding multiple datapipes can include a process of merging common data commonly applicableto a plurality of data pipes and data pipes related thereto and decodingthe same or a process of simultaneously decoding a plurality of servicesor service components (including a scalable video service) by theapparatus for receiving broadcast signals.

The output processor shown in FIG. 78 can include a BB descramblerblock, a padding removal block, a CRC-8 decoder block and a BB frameprocessor block as the output processor illustrated in FIG. 77. Thebasic roles of these blocks correspond to those of the blocks describedwith reference to FIG. 77 although operations thereof may differ fromthose of the blocks illustrated in FIG. 77.

A de-jitter buffer block 13000 included in the output processor shown inFIG. 78 can compensate for a delay, inserted by the apparatus fortransmitting broadcast signals for synchronization of multiple datapipes, according to a restored TTO (time to output) parameter.

A null packet insertion block 13100 can restore a null packet removedfrom a stream with reference to a restored DNP (deleted null packet) andoutput common data.

A TS clock regeneration block 13200 can restore time synchronization ofoutput packets based on ISCR (input stream time reference) information.

A TS recombining block 13300 can recombine the common data and datapipes related thereto, output from the null packet insertion block13100, to restore the original MPEG-TSs, IP streams (v4 or v6) orgeneric streams. The TTO, DNT and ISCR information can be obtainedthrough the BB frame header.

An in-band signaling decoding block 13400 can decode and output in-bandphysical layer signaling information transmitted through a padding bitfield in each FEC frame of a data pipe.

The output processor shown in FIG. 78 can BB-descramble the PLS-preinformation and PLS-post information respectively input through aPLS-pre path and a PLS-post path and decode the descrambled data torestore the original PLS data. The restored PLS data is delivered to asystem controller included in the apparatus for receiving broadcastsignals. The system controller can provide parameters necessary for thesynchronization & demodulation module, frame parsing module, demapping &decoding module and output processor module of the apparatus forreceiving broadcast signals.

The above-described blocks may be omitted or replaced by blocks havingsimilar r identical functions according to design.

FIG. 79 illustrates a coding & modulation module according to anotherembodiment of the present invention.

The coding & modulation module shown in FIG. 79 corresponds to anotherembodiment of the coding & modulation module illustrated in FIGS. 66 to70.

To control QoS for each service or service component transmitted througheach data pipe, as described above with reference to FIG. 70, the coding& modulation module shown in FIG. 79 can include a first block 14000 forSISO, a second block 14100 for MISO, a third block 14200 for MIMO and afourth block 14300 for processing the PLS-pre/PLS-post information. Inaddition, the coding & modulation module can include blocks forprocessing data pipes equally or differently according to the design.The first to fourth blocks 14000 to 14300 shown in FIG. 79 are similarto the first to fourth blocks 5000 to 5300 illustrated in FIG. 70.

However, the first to fourth blocks 14000 to 14300 shown in FIG. 79 aredistinguished from the first to fourth blocks 5000 to 5300 illustratedin FIG. 70 in that a constellation mapper 14010 included in the first tofourth blocks 14000 to 14300 has a function different from the first tofourth blocks 5000 to 5300 illustrated in FIG. 70, a rotation & I/Qinterleaver block 14020 is present between the cell interleaver and thetime interleaver of the first to fourth blocks 14000 to 14300illustrated in FIG. 79 and the third block 14200 for MIMO has aconfiguration different from the third block 5200 for MIMO illustratedin FIG. 70. The following description focuses on these differencesbetween the first to fourth blocks 14000 to 14300 shown in FIG. 79 andthe first to fourth blocks 5000 to 5300 illustrated in FIG. 70.

The constellation mapper block 14010 shown in FIG. 79 can map an inputbit word to a complex symbol. However, the constellation mapper block14010 may not perform constellation rotation, differently from theconstellation mapper block shown in FIG. 70. The constellation mapperblock 14010 shown in FIG. 79 is commonly applicable to the first, secondand third blocks 14000, 14100 and 14200, as described above.

The rotation & I/Q interleaver block 14020 can independently interleavein-phase and quadrature-phase components of each complex symbol ofcell-interleaved data output from the cell interleaver and output thein-phase and quadrature-phase components on a symbol-by-symbol basis.The number of number of input data pieces and output data pieces of therotation & I/Q interleaver block 14020 is two or more which can bechanged by the designer. In addition, the rotation & I/Q interleaverblock 14020 may not interleave the in-phase component.

The rotation & I/Q interleaver block 14020 is commonly applicable to thefirst to fourth blocks 14000 to 14300, as described above. In this case,whether or not the rotation & I/Q interleaver block 14020 is applied tothe fourth block 14300 for processing the PLS-pre/post information canbe signaled through the above-described preamble.

The third block 14200 for MIMO can include a Q-block interleaver block14210 and a complex symbol generator block 14220, as illustrated in FIG.79.

The Q-block interleaver block 14210 can permute a parity part of anFEC-encoded FEC block received from the FEC encoder. Accordingly, aparity part of an LDPC H matrix can be made into a cyclic structure likean information part. The Q-block interleaver block 14210 can permute theorder of output bit blocks having Q size of the LDPC H matrix and thenperform row-column block interleaving to generate final bit streams.

The complex symbol generator block 14220 receives the bit streams outputfrom the Q-block interleaver block 14210, maps the bit streams tocomplex symbols and outputs the complex symbols. In this case, thecomplex symbol generator block 14220 can output the complex symbolsthrough at least two paths. This can be modified by the designer.

The above-described blocks may be omitted or replaced by blocks havingsimilar or identical functions according to design.

The coding & modulation module according to another embodiment of thepresent invention, illustrated in FIG. 79, can output data pipes,PLS-pre information and PLS-post information processed for respectivepaths to the frame structure module.

FIG. 80 illustrates a demapping & decoding module according to anotherembodiment of the present invention.

The demapping & decoding module shown in FIG. 80 corresponds to anotherembodiment of the demapping & decoding module illustrated in FIG. 76.The demapping & decoding module shown in FIG. 80 can perform a reverseoperation of the operation of the coding & modulation module illustratedin FIG. 79.

As shown in FIG. 80, the demapping & decoding module according toanother embodiment of the present invention can include a first block15000 for SISO, a second block 11100 for MISO, a third block 15200 forMIMO and a fourth block 14300 for processing the PLS-pre/PLS-postinformation. In addition, the demapping & decoding module can includeblocks for processing data pipes equally or differently according todesign. The first to fourth blocks 15000 to 15300 shown in FIG. 80 aresimilar to the first to fourth blocks 11000 to 11300 illustrated in FIG.76.

However, the first to fourth blocks 15000 to 15300 shown in FIG. 80 aredistinguished from the first to fourth blocks 11000 to 11300 illustratedin FIG. 76 in that an I/Q deinterleaver and derotation block 15010 ispresent between the time interleaver and the cell deinterleaver of thefirst to fourth blocks 15000 to 15300, a constellation mapper 15010included in the first to fourth blocks 15000 to 15300 has a functiondifferent from the first to fourth blocks 11000 to 11300 illustrated inFIG. 76 and the third block 15200 for MIMO has a configuration differentfrom the third block 11200 for MIMO illustrated in FIG. 76. Thefollowing description focuses on these differences between the first tofourth blocks 15000 to 15300 shown in FIG. 80 and the first to fourthblocks 11000 to 11300 illustrated in FIG. 76.

The I/Q deinterleaver & derotation block 15010 can perform a reverseprocess of the process performed by the rotation & I/Q interleaver block14020 illustrated in FIG. 79. That is, the I/Q deinterleaver &derotation block 15010 can deinterleave I and Q componentsI/Q-interleaved and transmitted by the apparatus for transmittingbroadcast signals and derotate complex symbols having the restored I andQ components.

The I/Q deinterleaver & derotation block 15010 is commonly applicable tothe first to fourth blocks 15000 to 15300, as described above. In thiscase, whether or not the I/Q deinterleaver & derotation block 15010 isapplied to the fourth block 15300 for processing the PLS-pre/postinformation can be signaled through the above-described preamble.

The constellation demapper block 15020 can perform a reverse process ofthe process performed by the constellation mapper block 14010illustrated in FIG. 79. That is, the constellation demapper block 15020can demap cell-deinterleaved data without performing derotation.

The third block 15200 for MIMO can include a complex symbol parsingblock 15210 and a Q-block deinterleaver block 15220, as shown in FIG.80.

The complex symbol parsing block 15210 can perform a reverse process ofthe process performed by the complex symbol generator block 14220illustrated in FIG. 79. That is, the complex symbol parsing block 15210can parse complex data symbols and demap the same to bit data. In thiscase, the complex symbol parsing block 15210 can receive complex datasymbols through at least two paths.

The Q-block deinterleaver block 15220 can perform a reverse process ofthe process carried out by the Q-block interleaver block 14210illustrated in FIG. 79. That is, the Q-block deinterleaver block 15220can restore Q size blocks according to row-column deinterleaving,restore the order of permuted blocks to the original order and thenrestore positions of parity bits to original positions according toparity deinterleaving.

The above-described blocks may be omitted or replaced by blocks havingsimilar or identical functions according to design.

As illustrated in FIG. 80, the demapping & decoding module according toanother embodiment of the present invention can output data pipes andPLS information processed for respective paths to the output processor.

As described above, the apparatus and method for transmitting broadcastsignals according to an embodiment of the present invention canmultiplex signals of different broadcast transmission/reception systemswithin the same RF channel and transmit the multiplexed signals and theapparatus and method for receiving broadcast signals according to anembodiment of the present invention can process the signals in responseto the broadcast signal transmission operation. Accordingly, it ispossible to provide a flexible broadcast transmission and receptionsystem.

FIG. 81 is a table showing requirements of the broadcast signaltransmission/reception apparatus and method according to one embodimentof the present invention.

The first row of the table shown in FIG. 81 represents requirements ofthe broadcast signal transmission/reception apparatus and methodaccording to an embodiment of the present invention, the second rowrepresents values of the requirements, the third row represents detailsof the requirements and the fourth row shows technical solutions to therequirements.

As shown in the seventh column 16000 illustrated in FIG. 81, theapparatus for transmitting broadcast signals according to an embodimentof the present invention is a flexible system capable of providing afixed broadcast service like a terrestrial broadcast service, a portablebroadcast service like a mobile broadcast service and a broadcastservice having various qualities and purposes such as a UHD broadcastservice. In addition, the apparatus for transmitting broadcast signalsaccording to an embodiment of the present invention can multiplex dataof various broadcast services on a frame-by-frame basis and transmit themultiplexed data and the apparatus for receiving broadcast signalsaccording to an embodiment of the present invention can process receiveddata in response to the operation of the apparatus for transmittingbroadcast signals. Furthermore, the apparatus for transmitting broadcastsignals according to an embodiment of the present invention can controlQoS for each broadcast service in a physical layer stage, as describedabove.

As shown in the eighth column 16100 illustrated in FIG. 81, theapparatus for transmitting broadcast signals according to an embodimentof the present invention can provide a broadcast service using aportable antenna. Particularly, the apparatus for transmitting broadcastsignals according to an embodiment of the present invention can providea scalable video service composed of base layer data and enhancementlayer data for ultra HDTV and mobile HDTV broadcast services.

In addition, as shown in the tenth column 16200 illustrated in FIG. 81,the apparatus for transmitting broadcast signals and the apparatus forreceiving broadcast signals according to an embodiment of the presentinvention can provide an emergency alert system (EAS). Accordingly, theapparatus for transmitting broadcast signals according to an embodimentof the present invention can transmit an emergency alert system messageinformation (or an emergency alert message information) through aspecific data pipe in a signal frame in order to achieve fast access andhigher robust of the emergency alert system message information (or theemergency alert message information).

FIG. 82 illustrates a super-frame structure according to an embodimentof the present invention.

The apparatus for transmitting broadcast signals according to anembodiment of the present invention can sequentially transmit aplurality of super-frames carrying data corresponding to a plurality ofbroadcast services.

As shown in FIG. 82, frames 17100 of different types and a futureextension frame (FEF) 17110 can be multiplexed in the time domain andtransmitted in a super-frame 17000. The apparatus for transmittingbroadcast signals according to an embodiment of the present inventioncan multiplex signals of different broadcast services on aframe-by-frame basis and transmit the multiplexed signals in the same RFchannel, as described above. The different broadcast services mayrequire different reception conditions or different coverages accordingto characteristics and purposes thereof. Accordingly, signal frames canbe classified into types for transmitting data of different broadcastservices and data included in the signal frames can be processed bydifferent transmission parameters. In addition, the signal frames canhave different FFT sizes and guard intervals according to broadcastservices transmitted through the signal frames. The FEF 17110 shown inFIG. 82 is a frame available for future new broadcast service systems.

The signal frames 17100 of different types according to an embodiment ofthe present invention can be allocated to a super-frame according todesign. Specifically, the signal frames 17100 of different types can berepeatedly allocated to the super-frame in a multiplexed pattern.Otherwise, a plurality of signal frames of the same type can besequentially allocated to a super-frame and then signal frames of adifferent type can be sequentially allocated to the super-frame. Thesignal frame allocation scheme can be changed by the designer.

Each signal frame can include a preamble 17200, an edge data OFDM symbol17210 and a plurality of data OFDM symbols 17220, as shown in FIG. 82.

The preamble 17200 can carry signaling information related to thecorresponding signal frame, for example, a transmission parameter. Thatis, the preamble carries basic PLS data and is located in the beginningof a signal frame. In addition, the preamble 17200 can carry the PLSdata described with reference to FIG. 66. That is, the preamble cancarry only basic PLS data or both basic PLS data and the PLS datadescribed with reference to FIG. 66. The information carried through thepreamble can be changed by the designer. The signaling informationcarried through the preamble can be referred to as preamble signalinginformation.

The edge data OFDM symbol 17210 is an OFDM symbol located at thebeginning or end of the corresponding frame and can be used to transmitpilots in all pilot carriers of data symbols. The edge data OFDM symbolmay be in the form of a known data sequence or a pilot. The position ofthe edge data OFDM symbol 17210 can be changed by the designer.

The plurality of data OFDM symbols 17220 can carry data of broadcastservices.

Since the preamble 17200 illustrated in FIG. 82 includes informationindicating the start of each signal frame, the apparatus for receivingbroadcast signals according to an embodiment of the present inventioncan detect the preamble 17200 to perform synchronization of thecorresponding signal frame. Furthermore, the preamble 17200 can includeinformation for frequency synchronization and basic transmissionparameters for decoding the corresponding signal frame.

Accordingly, even if the apparatus for receiving broadcast signalsaccording to an embodiment of the present invention receives signalframes of different types multiplexed in a super-frame, the apparatusfor receiving broadcast signals can discriminate signal frames bydecoding preambles of the signal frames and acquire a desired broadcastservice.

That is, the apparatus for receiving broadcast signals according to anembodiment of the present invention can detect the preamble 17200 in thetime domain to check whether or not the corresponding signal is presentin the broadcast signal transmission and reception system according toan embodiment of the present invention. Then, the apparatus forreceiving broadcast signals according to an embodiment of the presentinvention can acquire information for signal frame synchronization fromthe preamble 17200 and compensate for a frequency offset. Furthermore,the apparatus for receiving broadcast signals according to an embodimentof the present invention can decode signaling information carried by thepreamble 17200 to acquire basic transmission parameters for decoding thecorresponding signal frame. Then, the apparatus for receiving broadcastsignals according to an embodiment of the present invention can obtaindesired broadcast service data by decoding signaling information foracquiring broadcast service data transmitted through the correspondingsignal frame.

FIG. 83 illustrates a preamble insertion block according to anembodiment of the present invention.

The preamble insertion block illustrated in FIG. 83 corresponds to anembodiment of the preamble insertion block 7500 described with referenceto FIG. 72 and can generate the preamble described in FIG. 82.

As shown in FIG. 83, the preamble insertion block according to anembodiment of the present invention can include a signaling sequenceselection block 18000, a signaling sequence interleaving block 18100, amapping block 18200, a scrambling block 18300, a carrier allocationblock 18400, a carrier allocation table block 18500, an IFFT block18600, a guard insertion block 18700 and a multiplexing block 18800.Each block may be modified or may not be included in the preambleinsertion block by the designer. A description will be given of eachblock of the preamble insertion block.

The signaling sequence selection block 18000 can receive the signalinginformation to be transmitted through the preamble and select asignaling sequence suitable for the signaling information.

The signaling sequence interleaving block 18100 can interleave signalingsequences for transmitting the input signaling information according tothe signaling sequence selected by the signaling sequence selectionblock 18000. Details will be described later.

The mapping block 18200 can map the interleaved signaling informationusing a modulation scheme.

The scrambling block 18300 can multiply mapped data by a scramblingsequence.

The carrier allocation block 18400 can allocate the data output from thescrambling block 18300 to predetermined carrier positions using activecarrier position information output from the carrier allocation tableblock 18500.

The IFFT block 18600 can transform the data allocated to carriers,output from the carrier allocation block 18400, into an OFDM signal inthe time domain.

The guard insertion block 18700 can insert a guard interval into theOFDM signal.

The multiplexing block 18800 can multiplex the signal output from theguard insertion block 18700 and a signal c(t) output from the guardsequence insertion block 7400 illustrated in FIG. 72 and output anoutput signal p(t). The output signal p(t) can be input to the waveformprocessing block 7600 illustrated in FIG. 72.

FIG. 84 illustrates a preamble structure according to an embodiment ofthe present invention.

The preamble shown in FIG. 84 can be generated by the preamble insertionblock illustrated in FIG. 83.

The preamble according to an embodiment of the present invention has astructure of a preamble signal in the time domain and can include ascrambled cyclic prefix part 19000 and an OFDM symbol 19100. Inaddition, the preamble according to an embodiment of the presentinvention may include an OFDM symbol and a scrambled cyclic postfixpart. In this case, the scrambled cyclic postfix part may follow theOFDM symbol, differently from the scrambled prefix, and may be generatedthrough the same process as the process for generating the scrambledcyclic prefix, which will be described later. The position andgeneration process of the scrambled cyclic postfix part may be changedaccording to design.

The scrambled cyclic prefix part 19000 shown in FIG. 84 can be generatedby scrambling part of the OFDM symbol or the whole OFDM symbol and canbe used as a guard interval.

Accordingly, the apparatus for receiving broadcast signals according toan embodiment of the present invention can detect a preamble throughguard interval correlation using a guard interval in the form of acyclic prefix even when a frequency offset is present in a receivedbroadcast signal since frequency synchronization cannot be performed.

In addition, the guard interval in the scrambled cyclic prefix formaccording to an embodiment of the present invention can be generated bymultiplying (or combining) the OFDM symbol by a scrambling sequence (orsequence). Or the guard interval in the scrambled cyclic prefix formaccording to an embodiment of the present invention can be generated byscrambling the OFDM symbol with a scrambling sequence (or sequence), Thescrambling sequence according to an embodiment of the present inventioncan be a signal of any type which can be changed by the designer.

The method of generating the guard interval in the scrambled cyclicprefix form according to an embodiment of the present invention has thefollowing advantages.

Firstly, a preamble can be easily detected by discriminating the guardinterval from a normal OFDM symbol. As described above, the guardinterval in the scrambled cyclic prefix form is generated by beingscrambled by the scrambling sequence, distinguished from the normal OFDMsymbol. In this case, if the apparatus for receiving broadcast signalsaccording to an embodiment of the present invention performs guardinterval correlation, the preamble can be easily detected since only acorrelation peak according to the preamble is generated without acorrelation peak according to the normal OFDM symbol.

Secondly, when the guard interval in the scrambled cyclic prefix formaccording to an embodiment of the present invention is used, a dangerousdelay problem can be solved. For example, if the apparatus for receivingbroadcast signals performs guard interval correlation when multi-pathinterference delayed by the duration Tu of the OFDM symbol is present,preamble detection performance may be deteriorated since a correlationvalue according to multiple paths is present at all times. However, whenthe apparatus for receiving broadcast signals according to an embodimentof the present invention performs guard interval correlation, theapparatus for receiving broadcast signals can detect the preamblewithout being affected by the correlation value according to multiplepaths since only a peak according to the scrambled cyclic prefix isgenerated, as described above.

Finally, the influence of continuous wave (CW) interference can beprevented. If a received signal includes CW interference, the signaldetection performance and synchronization performance of the apparatusfor receiving broadcast signals can be deteriorated since a DC componentcaused by CW is present at all times when the apparatus for receivingbroadcast signals performs guard interval correlation. However, when theguard interval in the scrambled cyclic prefix form according to anembodiment of the present invention is used, the influence of CW can beprevented since the DC component caused by CW is averaged out by thescrambling sequence.

FIG. 85 illustrates a preamble detector according to an embodiment ofthe present invention.

The preamble detector shown in FIG. 85 corresponds to an embodiment ofthe preamble detector 9300 included in the synchronization &demodulation module illustrated in FIG. 74 and can detect the preambleillustrated in FIG. 82.

As shown in FIG. 85, the preamble detector according to an embodiment ofthe present invention can include a correlation detector 20000, an FFTblock 20100, an ICFO (integer carrier frequency offset) estimator 20200,a carrier allocation table block 20300, a data extractor 20300 and asignaling decoder 20500. Each block may be modified or may not beincluded in the preamble detector according to design. A descriptionwill be given of operation of each block of the preamble detector.

The correlation detector 20000 can detect the above-described preambleand estimate frame synchronization, OFDM symbol synchronization, timinginformation and FCFO (fractional frequency offset). Details will bedescribed later.

The FFT block 20100 can transform the OFDM symbol part included in thepreamble into a frequency domain signal using the timing informationoutput from the correlation detector 20000.

The ICFO estimator 20200 can receive position information on activecarriers, output from the carrier allocation table block 20300, andestimate ICFO information.

The data extractor 20300 can receive the ICFO information output fromthe ICFO estimator 20200 to extract signaling information allocated tothe active carriers and the signaling decoder 20500 can decode theextracted signaling information.

Accordingly, the apparatus for receiving broadcast signals according toan embodiment of the present invention can obtain the signalinginformation carried by the preamble through the above-describedprocedure.

FIG. 86 illustrates a correlation detector according to an embodiment ofthe present invention.

The correlation detector shown in FIG. 86 corresponds to an embodimentof the correlation detector illustrated in FIG. 85.

The correlation detector according to an embodiment of the presentinvention can include a delay block 21000, a conjugate block 21100, amultiplier, a correlator block 21200, a peak search block 21300 and anFCFO estimator block 21400. A description will be given of operation ofeach block of the correlation detector.

The delay block 21000 of the correlation detector can delay an inputsignal r(t) by the duration Tu of the OFDM symbol in the preamble.

The conjugate block 21100 can perform conjugation on the delayed signalr(t).

The multiplier can multiply the signal r(t) by the conjugated signalr(t) to generate a signal m(t).

The correlator block 21200 can correlate the signal m(t) input theretoand the scrambling sequence to generate a descrambled signal c(t).

The peak search block 21300 can detect a peak of the signal c(t) outputfrom the correlator block 21200. In this case, since the scrambledcyclic prefix included in the preamble is descrambled by the scramblingsequence, a peak of the scrambled cyclic prefix can be generated.However, OFDM symbols or components caused by multiple paths other thanthe scrambled cyclic prefix are scrambled by the scrambling sequence,and thus a peak of the OFDM symbols or components caused by multiplepaths is not generated. Accordingly, the peak search block 21300 caneasily detect the peak of the signal c(t).

The FCFO estimator block 21400 can acquire frame synchronization andOFDM symbol synchronization of the signal input thereto and estimateFCFO information from a correlation value corresponding to the peak.

As described above, the scrambling sequence according to an embodimentof the present invention can be a signal of any type and can be changedby the designer.

FIGS. 87, 88 and 89 are graphs showing results obtained when achirp-like sequence, a balanced m-sequence and a Zadoff-Chu sequence areused as the scrambling sequence.

Each figure will now be described.

FIG. 87 shows graphs representing results obtained when the scramblingsequence according to an embodiment of the present invention is used.

The graph of FIG. 87 shows results obtained when the scrambling sequenceaccording to an embodiment of the present invention is a chirp-likesequence. The chirp-like sequence can be calculated according toExpression 1.e ^(j2πk/80) for k=0˜79,e ^(j2πk/144) for k=80˜223,e ^(j2πk/272) for k=224˜495,e ^(j2πk/528) for k=496˜1023  [Expression 1]

As represented by Expression 1, the chirp-like sequence can be generatedby connecting sinusoids of 4 different frequencies corresponding to oneperiod.

As shown in FIG. 87, (a) is a graph showing waveforms of the chirp-likesequence according to an embodiment of the present invention.

The first waveform 22000 shown in (a) represents a real number part ofthe chirp-like sequence and the second waveform 22100 represents animaginary number part of the chirp-like sequence. The duration of thechirp-like sequence corresponds to 1024 samples and the averages of areal number part sequence and an imaginary number part sequence are 0.

As shown in FIG. 87, (b) is a graph showing the waveform of the signalc(t) output from the correlator block illustrated in FIGS. 85 and 86when the chirp-like sequence is used.

Since the chirp-like sequence is composed of signals having differentperiods, dangerous delay is not generated. Furthermore, the correlationproperty of the chirp-like sequence is similar to guard intervalcorrelation and thus distinctly discriminated from the preamble ofconventional broadcast signal transmission/reception systems.Accordingly, the apparatus for receiving broadcast signals according toan embodiment of the present invention can easily detect the preamble.In addition, the chirp-like sequence can provide correct symbol timinginformation and is robust to noise on a multi-path channel, compared toa sequence having a delta-like correlation property, such as anm-sequence. Furthermore, when scrambling is performed using thechirp-like sequence, it is possible to generate a signal having abandwidth slightly increased compared to the original signal.

FIG. 88 shows graphs representing results obtained when a scramblingsequence according to another embodiment of the present invention isused.

The graphs of FIG. 88 are obtained when the balanced m-sequence is usedas a scrambling sequence. The balanced m-sequence according to anembodiment of the present invention can be calculated by Expression 2.g(x)=x ¹⁰ +x ⁸ +x ⁴ +x ³+1  [Expression 2]

The balanced m-sequence can be generated by adding a sample having avalue of ‘+1’ to an m-sequence having a length corresponding to 1023samples according to an embodiment of the present invention. The lengthof balanced m-sequence is 1024 samples and the average thereof is ‘0’according to one embodiment. The length and average of the balancedm-sequence can be changed by the designer.

As shown in FIG. 88, (a) is a graph showing the waveform of the balancedm-sequence according to an embodiment of the present invention and (b)is a graph showing the waveform of the signal c(t) output from thecorrelator block illustrated in FIGS. 85 and 86 when the balancedm-sequence is used.

When the balanced m-sequence according to an embodiment of the presentinvention is used, the apparatus for receiving broadcast signalsaccording to an embodiment of the present invention can easily performsymbol synchronization on a received signal since preamble correlationproperty corresponds to a delta function.

FIG. 89 shows graphs representing results obtained when a scramblingsequence according to another embodiment of the present invention isused.

The graphs of FIG. 89 show results obtained when the Zadoff-Chu sequenceis used as a scrambling sequence. The Zadoff-Chu sequence according toan embodiment of the present invention can be calculated by Expression3.e ^(−jπuk(k+1)/1023) for k=0˜1022, u=23  [Expression 3]

The Zadoff-Chu sequence may have a length corresponding to 1023 samplesand u value of 23 according to one embodiment. The length and u value ofthe Zadoff-Chu sequence can be changed by the designer.

As shown in FIG. 89, (a) is a graph showing the waveform of the signalc(t) output from the correlator block illustrated in FIGS. 85 and 86when the Zadoff-Chu sequence according to an embodiment of the presentinvention is used.

As shown in FIG. 89, (b) is a graph showing the in-phase waveform of theZadoff-Chu sequence according to an embodiment of the present inventionand (c) is a graph showing the quadrature phase waveform of theZadoff-Chu sequence according to an embodiment of the present invention.

When the Zadoff-Chu sequence according to an embodiment of the presentinvention is used, the apparatus for receiving broadcast signalsaccording to an embodiment of the present invention can easily performsymbol synchronization on a received signal since preamble correlationproperty corresponds to a delta function. In addition, the envelope ofthe received signal is uniform in both the frequency domain and timedomain.

FIG. 90 is a graph showing a result obtained when a scrambling sequenceaccording to another embodiment of the present invention is used.

The graph of FIG. 90 shows waveforms of a binary chirp-like sequence.The binary chirp-like sequence is an embodiment of the signal that canbe used as the scrambling sequence according to the present invention.

$\begin{matrix}{{x\lbrack k\rbrack} = \left\{ {{i\lbrack k\rbrack},{q\lbrack k\rbrack}} \right\}} & \left\lbrack {{Expression}\mspace{14mu} 4} \right\rbrack \\\begin{matrix}{{i\lbrack k\rbrack} = {{1\mspace{14mu}{for}\mspace{20mu} k} = {0 \sim 19}}} \\{= {{{- 1}\mspace{14mu}{for}\mspace{14mu} k} = {20 \sim 59}}} \\{= {{1\mspace{14mu}{for}\mspace{14mu} k} = {60 \sim 115}}} \\{= {{{- 1}\mspace{14mu}{for}\mspace{14mu} k} = {116 \sim 187}}} \\{= {{1\mspace{14mu}{for}\mspace{14mu} k} = {188 \sim 291}}} \\{= {{{- 1}\mspace{14mu}{for}\mspace{14mu} k} = {292 \sim 427}}} \\{= {{1\mspace{14mu}{for}\mspace{14mu} k} = {428 \sim 627}}} \\{= {{{- 1}\mspace{14mu}{for}\mspace{14mu} k} = {628 \sim 891}}} \\{= {{1\mspace{14mu}{for}\mspace{14mu} k} = {892 \sim 1023}}}\end{matrix} & \; \\\begin{matrix}{{q\lbrack k\rbrack} = {{1\mspace{14mu}{for}\mspace{14mu} k} = {0 \sim 39}}} \\{= {{{- 1}\mspace{14mu}{for}\mspace{14mu} k} = {40 \sim 79}}} \\{= {{1\mspace{14mu}{for}\mspace{14mu} k} = {80 \sim 151}}} \\{= {{{- 1}\mspace{14mu}{for}\mspace{14mu} k} = {152 \sim 223}}} \\{= {{1\mspace{14mu}{for}\mspace{14mu} k} = {224 \sim 359}}} \\{= {{{- 1}\mspace{14mu}{for}\mspace{14mu} k} = {360 \sim 495}}} \\{= {{1\mspace{14mu}{for}\mspace{14mu} k} = {496 \sim 759}}} \\{= {{{- 1}\mspace{14mu}{for}\mspace{14mu} k} = {760 \sim 1023}}}\end{matrix} & \;\end{matrix}$

The binary chirp-like sequence can be represented by Expression 4. Thesignal represented by Expression 4 is an embodiment of the binarychirp-like sequence.

The binary chirp-like sequence is a sequence that is quantized such thatthe real-number part and imaginary part of each signal valueconstituting the above-described chirp-like sequence have only twovalues of ‘1’ and ‘−1’. The binary chirp-like sequence according toanother embodiment of the present invention can have the real-numberpart and imaginary part having only two signal values of ‘−0.707 (−1divided by square root of 2)’ and ‘0.707’ (1 divided by square root of2). The quantized value of the real-number part and imaginary part ofthe binary chirp-like sequence can be changed by the designer. InExpression 4, i[k] represents the real-number part of each signalconstituting the sequence and q[k] represents the imaginary part of eachsignal constituting the sequence.

The binary chirp-like sequence has the following advantages. Firstly,the binary chirp-like sequence does not generate dangerous delay sinceit is composed of signals having different periods. Secondly, the binarychirp-like sequence has correlation characteristic similar to guardinterval correlation and thus provides correct symbol timing informationcompared to conventional broadcast systems and has higher noiseresistance on a multi-path channel than a sequence having delta-likecorrelation characteristic such as m-sequence. Thirdly, when scramblingis performed using the binary chirp-like sequence, bandwidth is lessincreased compared to the original signal. Fourthly, since the binarychirp-like sequence is a binary level sequence, a receiver with reducedcomplexity can be designed when the binary chirp-like sequence is used.

In the graph showing the waveforms of the binary chirp-like sequence, asolid line represents a waveform corresponding to real-number parts anda dotted line represents a waveform corresponding to imaginary parts.Both the waveforms of the real-number parts and imaginary parts of thebinary chirp-like sequence correspond to a square wave, differently fromthe chirp-like sequence.

FIG. 91 is a graph showing a result obtained when a scrambling sequenceaccording to another embodiment of the present invention is used.

The graph shows the waveform of signal c(t) output from theabove-described correlator block when the binary chirp-like sequence isused. In the graph, the peak may be a correlation peak according tocyclic prefix.

As described above with reference to FIG. 82, the signaling sequenceinterleaving block 18100 included in the preamble insertion blockaccording to an embodiment of the present invention can interleave thesignaling sequences for transmitting the input signaling informationaccording to the signaling sequence selected by the signaling sequenceselection block 18000.

A description will be given of a method through which the signalingsequence interleaving block 18100 according to an embodiment of thepresent invention interleaves the signaling information in the frequencydomain of the preamble.

FIG. 92 illustrates a signaling information interleaving procedureaccording to an embodiment of the present invention.

The preamble according to an embodiment of the present invention,described above with reference to FIG. 82, can have a size of 1K symboland only 384 active carriers from among carriers constituting the 1Ksymbol can be used. The size of the preamble or the number of activecarriers used can be changed by the designer. The signalling datacarried in the preamble is composed of 2 signalling fields, namely S1and S2.

As shown in FIG. 92, the signaling information carried by the preambleaccording to an embodiment of the present invention can be transmittedthrough bit sequences of S1 and bit sequences of S2.

The bit sequences of S1 and the bit sequences of S2 according to anembodiment of the present invention represent signaling sequences thatcan be allocated to active carriers to respectively carry signalinginformation (or signaling fields) included in the preamble.

Specifically, S1 can carry 3-bit signaling information and can beconfigured in a structure in which a 64-bit sequence is repeated twice.In addition, S1 can be located before and after S2. S2 is a single256-bit sequence and can carry 4-bit signaling information. The bitsequences of S1 and S2 are represented as sequential numbers startingfrom 0 according to an embodiment of the present invention. Accordingly,the first bit sequence of S1 can be represented as S1(0) and the firstbit sequence of S2 can be represented as S2(0), as shown in FIG. 92.This can be changed by the designer.

S1 can carry information for identifying the signal frames included inthe super-frame described in FIG. 81, for example, a signal frameprocessed according to SISO, a signal frame processed according to MISOor information indicating FE. S2 can carry information about the FFTsize of the current signal frame, information indicating whether or notframes multiplexed in a super-frame are of the same type or the like.Information that can be carried by S1 and S2 can be changed according todesign.

As shown in FIG. 92, the signaling sequence interleaving block 18100according to an embodiment of the present invention can sequentiallyallocate S1 and S2 to active carriers corresponding to predeterminedpositions in the frequency domain.

In one embodiment of the present invention, 384 carriers are present andare represented as sequential numbers starting from 0. Accordingly, thefirst carrier according to an embodiment of the present invention can berepresented as a(0), as shown in FIG. 92. In FIG. 92, uncolored activecarriers are null carriers to which S1 or S2 is not allocated from amongthe 384 carriers.

As illustrated in FIG. 92, bit sequences of S1 can be allocated toactive carriers other than null carriers from among active carriers a(0)to a(63), bit sequences of S2 can be allocated to active carriers otherthan null carriers from among active carriers a(64) to a(319) and bitsequences of S1 can be allocated to active carriers other than nullcarriers from among active carriers a(320) to a(383).

According to the interleaving method illustrated in FIG. 92, theapparatus for receiving broadcast signals may not decode specificsignaling information affected by fading when frequency selective fadingoccurs due to multi-path interference and a fading period isconcentrated on a region to which the specific signaling information isallocated.

FIG. 93 illustrates a signaling information interleaving procedureaccording to another embodiment of the present invention.

According to the signaling information interleaving procedureillustrated in FIG. 93, the signaling information carried by thepreamble according to an embodiment of the present invention can betransmitted through bit sequences of S1, bit sequences of S2 and bitsequences of S3. The signalling data carried in the preamble is composedof 3 signalling fields, namely S1, S2 and S3.

As illustrated in FIG. 93, the bit sequences of S1, the bit sequences ofS2 and the bit sequences of S3 according to an embodiment of the presentinvention are signaling sequences that can be allocated to activecarriers to respectively carry signaling information (or signalingfields) included in the preamble.

Specifically, each of S1, S2 and S3 can carry 3-bit signalinginformation and can be configured in a structure in which a 64-bitsequence is repeated twice. Accordingly, 2-bit signaling information canbe further transmitted compared to the embodiment illustrated in FIG.92.

In addition, S1 and S2 can respectively carry the signaling informationdescribed in FIG. 92 and S3 can carry signaling information about aguard length (or guard interval length). Signaling information carriedby S1, S2 and S3 can be changed according to design.

As illustrated in FIG. 93, bit sequences of S1, S2 and S3 can berepresented as sequential numbers starting from 0, that is, S1(0), . . .. In the present embodiment of the invention, 384 carriers are presentand are represented as sequential numbers starting from 0, that is,b(0), . . . . This can be modified by the designer.

As illustrated in FIG. 93, S1, S2 and S3 can be sequentially andrepeatedly allocated to active carriers corresponding to predeterminedpositions in the frequency domain.

Specifically, bit sequences of S1, S2 and S3 can be sequentiallyallocated to active carriers other than null packets from among activecarriers b(0) to b(383) according to Expression 5.b(n)=S1(n/3) when n mod 3=0 and 0≦n<192b(n)=S2((n−1)/3) when n mod 3=1 and 0≦n<192b(n)=S3((n−2)/3) when n mod 3=2 and 0≦n<192b(n)=S1((n−192)/3) when n mod 3=0 and 192≦n<384b(n)=S2((n−192−1)/3) when n mod 3=1 and 192≦n<384b(n)=S3((n−192−2)/3) when n mod 3=2 and 192≦n<384  [Expression 5]

According to the interleaving method illustrated in FIG. 93, it ispossible to transmit a larger amount of signaling information than theinterleaving method illustrated in FIG. 92. Furthermore, even iffrequency selective fading occurs due to multi-path interference, theapparatus for receiving broadcast signals can uniformly decode signalinginformation since a fading period can be uniformly distributed in aregion to which signaling information is allocated.

FIG. 94 illustrates a signaling decoder according to an embodiment ofthe present invention.

The signaling decoder illustrated in FIG. 94 corresponds to anembodiment of the signaling decoder illustrated in FIG. 84 and caninclude a descrambler 27000, a demapper 27100, a signaling sequencedeinterleaver 27200 and a maximum likelihood detector 27300. Adescription will be given of operation of each block of the signalingdecoder.

The descrambler 27000 can descramble a signal output from the dataextractor. In this case, the descrambler 27000 can perform descramblingby multiplying the signal output from the data extractor by thescrambling sequence. The scrambling sequence according to an embodimentof the present invention can correspond to one of the sequencesdescribed with reference to FIGS. 87 to 91.

The demapper 27100 can demap the signal output from the descrambler27000 to output sequences having a soft value.

The signaling sequence deinterleaver 27200 can rearrange uniformlyinterleaved sequences as consecutive sequences in the original order byperforming deinterleaving corresponding to a reverse process of theinterleaving process described in FIGS. 92 and 93.

The maximum likelihood detector 27300 can decode preamble signalinginformation using the sequences output from the signaling sequencedeinterleaver 27200.

FIG. 95 is a graph showing the performance of the signaling decoderaccording to an embodiment of the present invention.

The graph of FIG. 95 shows the performance of the signaling decoder asthe relationship between correct decoding probability and SNR in thecase of perfect synchronization, 1 sample delay, 0 dB and 270 degreesingle ghost.

Specifically, first, second and third curves 28000 respectively show thedecoding performance of the signaling decoder for S1, S2 and S3 when theinterleaving method illustrated in FIG. 92 is employed, that is, S1, S2and S3 are sequentially allocated to active carriers and transmitted.Fourth, fifth and sixth curves 28100 respectively show the decodingperformance of the signaling decoder for S1, S2 and S3 when theinterleaving method illustrated in FIG. 93 is employed, that is, S1, S2and S3 are sequentially allocated to active carriers corresponding topredetermined positions in the frequency domain in a repeated manner andtransmitted. Referring to FIG. 95, it can be known that there is a largedifference between signaling decoding performance for a regionconsiderably affected by fading and signaling decoding performance for aregion that is not affected by fading when a signal processed accordingto the interleaving method illustrated in FIG. 92 is decoded. When asignal processed according to the interleaving method illustrated inFIG. 93 is decoded, however, uniform signaling decoding performance isachieved for S1, S2 and S3.

FIG. 96 illustrates a preamble insertion block according to anotherembodiment of the present invention.

The preamble insertion block shown in FIG. 96 corresponds to anotherembodiment of the preamble insertion block 7500 illustrated in FIGS. 72and 83.

As shown in FIG. 96, the preamble insertion block can include a ReedMuller encoder 29000, a data formatter 29100, a cyclic delay block29200, an interleaver 29300, a DQPSK (differential quadrature phaseshift keying)/DBPSK (differential binary phase shift keying) mapper29400, a scrambler 29500, a carrier allocation block 29600, a carrierallocation table block 29700, an IFFT block 29800, a scrambled guardinsertion block 29900, a preamble repeater 29910 and a multiplexingblock 29920. Each block may be modified or may not be included in thepreamble insertion block according to design. A description will begiven of operation of each block of the preamble insertion block.

The Reed Muller encoder 29000 can receive signaling information to becarried by the preamble and perform Reed Muller encoding on thesignaling information. When Reed Muller encoding is performed,performance can be improved compared to signaling using an orthogonalsequence or signaling using the sequence described in FIG. 82.

The data formatter 29100 can receive bits of the signaling informationon which Reed Muller encoding has been performed and format the bits torepeat and arrange the bits.

The DQPSK/DBPSK mapper 29400 can map the formatted bits of the signalinginformation according to DQPSK or DBPSK and output the mapped signalinginformation.

When the DQPSK/DBPSK mapper 29400 maps the formatted bits of thesignaling information according to DBPSK, the operation of the cyclicdelay block 29200 can be omitted. The interleaver 29300 can receive theformatted bits of the signaling information and perform frequencyinterleaving on the formatted bits of the signaling information tooutput interleaved data. In this case, the operation of the interleavercan be omitted according to design.

When the DQPSK/DBPSK mapper 29400 maps the formatted bits of thesignaling information according to DQPSK, the data formatter 29100 canoutput the formatted bits of the signaling information to theinterleaver 29300 through path I shown in FIG. 96.

The cyclic delay block 29200 can perform cyclic delay on the formattedbits of the signaling information output from the data formatter 29100and then output the cyclic-delayed bits to the interleaver 29300 throughpath Q shown in FIG. 95. When cyclic Q-delay is performed, performanceon a frequency selective fading channel is improved.

The interleaver 29300 can perform frequency interleaving on thesignaling information received through paths I and Q and the cyclicQ-delayed signaling information to output interleaved information. Inthis case, the operation of the interleaver 29300 can be omittedaccording to design.

Expressions 6 and 7 represent the relationship between input informationand output information or a mapping rule when the DQPSK/DBPSK mapper29400 maps the signaling information input thereto according to DQPSKand DBPSK.

As shown in FIG. 96, the input information of the DQPSK/DBPSK mapper29400 can be represented as s_(i)[in] and s_(q)[n] and the outputinformation of the DQPSK/DBPSK mapper 29400 can be represented asm_(i)[in] and m_(q)[n].m _(i)[−1]=1,m _(i) [n]=m _(i) [n−1] if s _(i) [n]=0m _(i) [n]=−m _(i) [n−1] if s _(i) [n]=1,m _(g) [n]=0, n=0˜1,1: # of Reed Muller encoded signalingbits  [Expression 6]y[−1]=0y[n]=y[n−1] if s _(i) [n]=0 and s _(q) [n]=0y[n]=(y[n−1]+3)mod 4 if s _(i) [n]=0 and s _(q) [n]=1y[n]=(y[n−1]+1)mod 4 if s _(i) [n]=1 and s _(q) [n]=0y[n]=(y[n−1]+2)mod 4 if s _(i) [n]=1 and s _(q) [n]=1, n=0˜1,1: # ofReed Muller encoded signalling bitsm _(i) [n]=1/√{square root over (2)} m _(q) [n]=1/√{square root over(2)} if y[n]=0m _(i) [n]=−1/√{square root over (2)} m _(q) [n]=1/√{square root over(2)} if y[n]=1m _(i) [n]=−1/√{square root over (2)} m _(q) [n]=−1/√{square root over(2)} if y[n]=2m _(i) [n]=1/√{square root over (2)} m _(q) [n]=−1/√{square root over(2)} if y[n]=3, n=1˜1,1: # of Reed Muller encoded signalingbits  [Expression 7]

The scrambler 29500 can receive the mapped signaling information outputfrom the DQPSK/DBPSK mapper 29400 and multiply the signaling informationby the scrambling sequence.

The carrier allocation block 29600 can allocate the signalinginformation processed by the scrambler 29500 to predetermined carriersusing position information output from the carrier allocation tableblock 29700.

The IFFT block 29800 can transform the carriers output from the carrierallocation block 29600 into an OFDM signal in the time domain.

The scrambled guard insertion block 29900 can insert a guard intervalinto the OFDM signal to generate a preamble. The guard intervalaccording to one embodiment of the present invention can correspond tothe guard interval in the scrambled cyclic prefix form described in FIG.83 and can be generated according to the method described in FIG. 83.

The preamble repeater 29910 can repeatedly arrange the preamble in asignal frame. The preamble according to one embodiment of the presentinvention can have the preamble structure described in FIG. 83 and canbe transmitted through one signal frame only once.

When the preamble repeater 29910 repeatedly allocate the preamble withinone signal frame, the OFDM symbol region and scrambled cyclic prefixregion of the preamble can be separated from each other. The preamblecan include the scrambled cyclic prefix region and the OFDM symbolregion, as described above. In the specification, the preamblerepeatedly allocated by the preamble repeater 29910 can also be referredto as a preamble. The repeated preamble structure may be a structure inwhich the OFDM symbol region and the scrambled cyclic prefix region arealternately repeated. Otherwise, the repeated preamble structure may bea structure in which the OFDM symbol region is allocated, the scrambledprefix region is consecutively allocated twice or more and then the OFDMsymbol region is allocated. Furthermore, the repeated preamble structuremay be a structure in which the scrambled cyclic prefix region isallocated, the OFDM symbol region is consecutively allocated twice ormore and then the scrambled cyclic prefix region is allocated. Apreamble detection performance level can be controlled by adjusting thenumber of repetitions of the OFDM symbol region or scrambled cyclicprefix region and positions in which the OFDM symbol region andscrambled cyclic prefix region are allocated.

When the same preamble is repeated in one frame, the apparatus forreceiving broadcast signals can stably detect the preamble even in thecase of low SNR and decode the signaling information.

The multiplexing block 29920 can multiplex the signal output from thepreamble repeater 29910 and the signal c(t) output from the guardsequence insertion block 7400 illustrated in FIG. 72 to output an outputsignal p(t). The output signal p(t) can be input to the waveformprocessing block 7600 described in FIG. 72.

FIG. 97 illustrates a structure of signaling data in a preambleaccording to an embodiment of the present invention.

Specifically, FIG. 97 shows the structure of the signaling data carriedon the preamble according to an embodiment of the present invention inthe frequency domain.

As shown in FIG. 97, (a) and (b) illustrate an embodiment in which thedata formatter 29100 described in FIG. 96 repeats or allocates dataaccording to code block length of Reed Muller encoding performed by theReed Muller encoder 29000.

The data formatter 29100 can repeat the signaling information outputfrom the Reed Muller encoder 29000 such that the signaling informationcorresponds to the number of active carriers based on code block lengthor arrange the signaling information without repeating the same. (a) and(b) correspond to a case in which the number of active carriers is 384.

Accordingly, when the Reed Muller encoder 29000 performs Reed Mullerencoding of a 64-bit block, as shown in (a), the data formatter 29100can repeat the same data six times. In this case, if the first orderReed Muller code is used in Reed Muller encoding, the signaling data maybe 7 bits.

When the Reed Muller encoder 29000 performs Reed Muller encoding of a256-bit block, as shown in (b), the data formatter 29100 can repeatformer 128 bits or later 124 bits of the 256-bit code block or repeat128 even-numbered bits or 124 odd-numbered bits. In this case, if thefirst order Reed Muller code is used in Reed Muller encoding, thesignaling data may be 8 bits.

As described above with reference to FIG. 96, the signaling informationformatted by the data formatter 29100 can be processed by the cyclicdelay block 29200 and the interleaver 29300 or mapped by the DQPSK/DBPSKmapper 29400 without being processed by the cyclic delay block 29200 andthe interleaver 29300, scrambled by the scrambler 29500 and input to thecarrier allocation block 29600.

As shown in FIG. 97, (c) illustrates a method of allocating thesignaling information to active carriers in the carrier allocation block29600 according to one embodiment. As shown in (c), b(n) representscarriers to which data is allocated and the number of carriers can be384 in one embodiment of the present invention. Colored carriers fromamong the carriers shown in (c) refer to active carriers and uncoloredcarriers refer to null carriers. The positions of the active carriersillustrated in (c) can be changed according to design.

FIG. 98 illustrates a procedure of processing signaling data carried ona preamble according to one embodiment.

The signaling data carried on a preamble may include a plurality ofsignaling sequences. Each signaling sequence may be 7 bits. The numberand size of signaling sequences can be changed by the designer.

In the figure, (a) illustrates a signaling data processing procedureaccording to an embodiment when the signaling data carried on thepreamble is 14 bits. In this case, the signaling data carried on thepreamble can include two signaling sequences which are respectivelyreferred to as signaling 1 and signaling 2. Signaling 1 and signaling 2may correspond to the above-described signaling sequences S1 and S2.

Each of signaling 1 and signaling 2 can be encoded into a 64-bit ReedMuller code by the above-described Reed Muller encoder. In the figure,(a) illustrates Reed Muller encoded signaling sequence blocks 32010 and32040.

The signaling sequence blocks 32010 and 32040 of the encoded signaling 1and signaling 2 can be repeated three times by the above-described dataformatter. In the figure, (a) illustrates repeated signaling sequenceblocks 32010, 32020 and 32030 of signaling 1 and repeated signalingsequence blocks 32040, 32050 and 32060 of repeated signaling 2. Since aReed-Muller encoded signaling sequence block is 64 bits, each of thesignaling sequence blocks of signaling 1 and signaling 2, which arerepeated three times, is 192 bits.

Signaling 1 and signaling 2 composed of 6 blocks 32010, 32020, 32030,32040, 32050 and 32060 can be allocated to 384 carriers by theabove-described carrier allocation block. In the figure (a), b(0) is thefirst carrier and b(1) and b(2) are carriers. 384 carriers b(0) tob(383) are present in one embodiment of the present invention. Coloredcarriers from among the carriers shown in the figure refer to activecarriers and uncolored carriers refer to null carriers. The activecarrier represents a carrier to which signaling data is allocated andthe null carrier represents a carrier to which signaling data is notallocated. In this specification, active carrier can also be referred toas a carrier. Data of signaling 1 and data of signaling 2 can bealternately allocated to carriers. For example, the data of signaling 1can be allocated to b(0), the data of signaling 2 can be allocated tob(7) and the data of signaling 1 can be allocated to b(24). Thepositions of the active carriers and null carriers can be changed by thedesigner.

In the figure, (b) illustrates a signaling data processing procedurewhen the signaling data transmitted through the preamble is 21 bits. Inthis case, the signaling data transmitted through the preamble caninclude three signaling sequences which are respectively referred to assignaling 1, signaling 2 and signaling 3. Signaling 1, signaling 2 andsignaling 3 may correspond to the above-described signaling sequencesS1, S2 and S3.

Each of signaling 1, signaling 2 and signaling 3 can be encoded into a64-bit Reed-Muller code by the above-described Reed-Muller encoder. Inthe figure, (b) illustrates Reed-Muller encoded signaling sequenceblocks 32070, 32090 and 32110.

The signaling sequence blocks 32070, 32090 and 32110 of the encodedsignaling 1, signaling 2 and signaling 3 can be repeated twice by theabove-described data formatter. In the figure, (b) illustrates therepeated signaling sequence blocks 32070 and 32080 of signaling 1,repeated signaling sequence blocks 32090 and 32100 of signaling 2 andrepeated signaling sequence blocks 32110 and 32120 of signaling 3. Sincea Reed-Muller encoded signaling sequence block is 64 bits, each of thesignaling sequence blocks of signaling 1, signaling 2 and signaling 3,which are repeated twice, is 128 bits.

Signaling 1, signaling 2 and signaling 3 composed of 6 blocks 32070,32080, 32090, 32100, 32110 and 32120 can be allocated to 384 carriers bythe above-described carrier allocation block. In the figure (b), b(0) isthe first carrier and b(1) and b(2) are carriers. 384 carriers b(0) tob(383) are present in one embodiment of the present invention. Coloredcarriers from among the carriers shown in the figure refer to activecarriers and uncolored carriers refer to null carriers. The activecarrier represents a carrier to which signaling data is allocated andthe null carrier represents a carrier to which signaling data is notallocated. Data of signaling 1, signaling 2 and data of signaling 3 canbe alternately allocated to carriers. For example, the data of signaling1 can be allocated to b(0), the data of signaling 2 can be allocated tob(7), the data of signaling 3 can be allocated to b(24) and the data ofsignaling 1 can be allocated to b(31). The positions of the activecarriers and null carriers can be changed by the designer.

As illustrated in (a) and (b) of the figure, trade off between signalingdata capacity and signaling data protection level can be achieved bycontrolling the length of an FEC encoded signaling data block. That is,when the signaling data block length increases, signaling data capacityincreases whereas the number of repetitions by the data formatter andthe signaling data protection level decrease. Accordingly, varioussignaling capacities can be selected.

FIG. 99 illustrates a preamble structure repeated in the time domainaccording to one embodiment.

As described above, the preamble repeater can alternately repeat dataand a scrambled guard interval. In the following description, a basicpreamble refers to a structure in which a data region follows ascrambled guard interval.

In the figure, (a) illustrates a structure in which the basic preambleis repeated twice in a case in which the preamble length is 4N. Since apreamble having the structure of (a) includes the basic preamble, thepreamble can be detected even by a normal receiver in an environmenthaving a high signal-to-noise ratio (SNR) and detected using therepeated structure in an environment having a low SNR. The structure of(a) can improve decoding performance of the receiver since signalingdata is repeated in the structure.

In the figure, (b) illustrates a preamble structure when the preamblelength is 5N. The structure of (b) is started with data and then a guardinterval and data are alternately allocated. This structure can improvepreamble detection performance and decoding performance of the receiversince the data is repeated a larger number of times (3N) than thestructure of (a).

In the figure, (c) illustrates a preamble structure when the preamblelength is 5N. Distinguished from the structure of (b), the structure of(c) is started with the guard interval and then the data and the guardinterval are alternately allocated. The structure of (c) has a smallernumber (2N) of repetitions of data than the structure of (b) althoughthe preamble length is identical to that of the structure of (b), andthus the structure of (c) may deteriorate decoding performance of thereceiver. However, the preamble structure of (c) has an advantage that aframe is started in the same manner as a normal frame since the dataregion follows the scrambled guard interval.

FIG. 100 illustrates a preamble detector and a correlation detectorincluded in the preamble detector according to an embodiment of thepresent invention.

FIG. 100 illustrates an embodiment of the above-described preambledetector for the preamble structure of (b) in the above-described figureshowing the preamble structure repeated in the time domain.

The preamble detector according to the present embodiment can include acorrelation detector 34010, an FFT block 34020, an ICFO estimator 34030,a data extractor 34040 and/or a signaling decoder 34050.

The correlation detector 34010 can detect a preamble. The correlationdetector 34010 can include two branches. The above-described repeatedpreamble structure can be a structure in which the scrambled guardinterval and data region are alternatively assigned. Branch 1 can beused to obtain correlation of a period in which the scrambled guardinterval is located prior to the data region in the preamble. Branch 2can be used to obtain correlation of a period in which the data regionis located prior to the scrambled guard interval in the preamble.

In the preamble structure of (b) in the above figure showing thepreamble structure repeated in the time domain, in which the data regionand scrambled guard interval are repeated, the period in which thescrambled guard interval is located prior to the data region appearstwice and the period in which the data region is located prior to thescrambled guard interval appears twice. Accordingly, 2 correlation peakscan be generated in each of branch 1 and branch 2. The 2 correlationbranches generated in each branch can be summed. A correlator includedin each branch can correlate the summed correlation peak with ascrambling sequence. The correlated peaks of branch 1 and branch 2 canbe summed and a peak detector can detect the preamble position from thesummed peak of branch 1 and branch 2 and perform OFDM symbol timingsynchronization and fractional frequency offset synchronization.

The FFT block 34020, ICFO estimator 34030, data extractor 34040 andsignaling decoder 34050 can operate in the same manner as theabove-described corresponding blocks.

FIG. 101 illustrates a preamble detector according to another embodimentof the present invention.

The preamble detector shown in FIG. 101 corresponds to anotherembodiment of the preamble detector 9300 described in FIGS. 74 and 85and can perform operation corresponding to the preamble insertion blockillustrated in FIG. 96.

As shown in FIG. 101, the preamble detector according to anotherembodiment of the present invention can include a correlation detector,an FFT block, an ICFO estimator, a carrier allocation table block, adata extractor and a signaling decoder 31100 in the same manner as thepreamble detector described in FIG. 85. However, the preamble detectorshown in FIG. 101 is distinguished from the preamble detector shown inFIG. 85 in that the preamble detector shown in FIG. 101 includes apreamble combiner 31000. Each block may be modified or omitted from thepreamble detector according to design.

Description of the same blocks as those of the preamble detectorillustrated in FIG. 85 is omitted and operations of the preamblecombiner 31000 and signaling decoder 31100 are described.

The preamble combiner 31000 can include n delay blocks 31010 and anadder 31020. The preamble combiner 31000 can combine received signals toimprove signal characteristics when the preamble repeater 29910described in FIG. 95 repeatedly allocate the same preamble to one signalframe.

As shown in FIG. 101, the n delay blocks 31010 can delay each preambleby p*n−1 in order to combine repeated preambles. In this case, prepresents a preamble length and n represents the number of repetitions.

The adder 31020 can combine the delayed preambles.

The signaling decoder 31100 corresponds to another embodiment of thesignaling decoder illustrated in FIG. 96 and can perform reverseoperations of the operations of the Reed Muller encoder 29000, dataformatter 29100, cyclic delay block 29200, interleaver 29300,DQPSK/DBPSK mapper 29400 and scrambler 29500 included in the preambleinsertion block illustrated in FIG. 96.

As shown in FIG. 101, the signaling decoder 31100 can include adescrambler 31110, a differential decoder 31120, a deinterleaver 31130,a cyclic delay block 31140, an I/Q combiner 31150, a data deformatter31160 and a Reed Muller decoder 31170.

The descrambler 31110 can descramble a signal output from the dataextractor.

The differential decoder 31120 can receive the descrambled signal andperform DBPSK or DQPSK demapping on the descrambled signal.

Specifically, when a signal on which DQPSK mapping has been performed inthe apparatus for transmitting broadcast signals is received, thedifferential decoder 31120 can phase-rotate a differential-decodedsignal by π/4. Accordingly, the differential decoded signal can bedivided into in-phase and quadrature components.

If the apparatus for transmitting broadcast signals has performedinterleaving, the deinterleaver 31130 can deinterleave the signal outputfrom the differential decoder 31120.

If the apparatus for transmitting broadcast signals has performed cyclicdelay, the cyclic delay block 31140 can perform a reverse process ofcyclic delay.

The I/Q combiner 31150 can combine I and Q components of thedeinterleaved or delayed signal.

If a signal on which DBPSK mapping has been performed in the apparatusfor transmitting broadcast signals is received, the I/Q combiner 31150can output only the I component of the deinterleaved signal.

The data deformatter 31160 can combine bits of signals output from theI/Q combiner 31150 to output signaling information. The Reed Mullerdecoder 31170 can decode the signaling information output from the datadeformatter 31160.

Accordingly, the apparatus for receiving broadcast signals according toan embodiment of the present invention can acquire the signalinginformation carried by the preamble through the above-describedprocedure.

FIG. 102 illustrates a preamble detector and a signaling decoderincluded in the preamble detector according to an embodiment of thepresent invention.

FIG. 102 shows an embodiment of the above-described preamble detector.

The preamble detector according to the present embodiment can include acorrelation detector 36010, an FFT block 36020, an ICFO estimator 36030,a data extractor 36040 and/or a signaling decoder 36050.

The correlation detector 36010, FFT block 36020, ICFO estimator 36030and data extractor 36040 can perform the same operations as those of theabove-described corresponding blocks.

The signaling decoder 36050 can decode the preamble. The signalingdecoder 36050 according to the present embodiment can include a dataaverage module 36051, a descrambler 36052, a differential decoder 36053,a deinterleaver 36054, a cyclic delay 36055, an I/Q combiner 36056, adata deformatter 36057 and/or a Reed-Muller decoder 36058.

The data average module 36051 can calculate the average of repeated datablocks to improve signal characteristics when the preamble has repeateddata blocks. For example, if a data block is repeated three times, asillustrated in (b) of the above figure showing the preamble structurerepeated in the time domain, the data average module 36051 can calculatethe average of the 3 data blocks to improve signal characteristics. Thedata average module 36051 can output the averaged data to the nextmodule.

The descrambler 36052, differential decoder 36053, deinterleaver 36054,cyclic delay 36055, I/Q combiner 36056, data deformatter 36057 and ReedMuller decoder 36058 can perform the same operations as those of theabove-described corresponding blocks.

FIG. 103 is a flowchart illustrating a method for transmitting broadcastsignals according to an embodiment of the present invention.

The apparatus for transmitting broadcast signals according to anembodiment of the present invention can encode DP (Data Pipe) datacarrying at least one service (S38000). As described above, a data pipeis a logical channel in the physical layer that carries service data orrelated metadata, which may carry one or multiple service(s) or servicecomponent(s). Data carried by a data pipe can be referred to as DP data.The detailed process of step S38000 is as described in FIG. 66, 70 or79.

The apparatus for transmitting broadcast signals according to anembodiment of the present invention can map the encoded DP data ontoconstellations (S38100). The detailed process of this step is asdescribed in FIG. 66, 70 or 79.

Then, the apparatus for transmitting broadcast signals according to anembodiment of the present invention can time-interleave the mapped DPdata (S38200). The detailed process of this step is as described in FIG.66, 70 or 79.

Subsequently, the apparatus for transmitting broadcast signals accordingto an embodiment of the present invention can build a signal frameincluding the time-interleaved DP data (S38300). The detailed process ofthis step is as described in FIG. 66 or 71.

The apparatus for transmitting broadcast signals according to anembodiment of the present invention can modulate data included in thebuilt signal frame using an OFDM scheme (S38400). The detailed processof this step is as described in FIG. 66 or 72.

The apparatus for transmitting broadcast signals according to anembodiment of the present invention can transmit broadcast signalsincluding the signal frame (S38500). The detailed process of this stepis as described in FIG. 66 or 72.

As described above, the signal frame according to an embodiment of thepresent invention can include emergency alert system (EAS, or emergencyalert message) information. In this case, the EAS information can betransmitted through a specific data pipe in the signal frame accordingto design.

In addition, the apparatus for transmitting broadcast signals accordingto an embodiment of the present invention can multiplex signals ofdifferent broadcast services on a frame-by-frame basis and transmit thesame in the same RF channel. The different broadcast services mayrequire different reception conditions or different coverages accordingto characteristics and purposes thereof. Accordingly, signal frames canbe classified into types for transmitting data of different broadcastservices and data included in the respective signal frames can beprocessed by different transmission parameters. Furthermore, the signalframes can have different FFT sizes and guard intervals according tobroadcast services transmitted therethrough. In this case, the apparatusfor transmitting broadcast signals according to an embodiment of thepresent invention can generate a preamble and insert the same in eachsignal frame, as described above. The preamble carriers basic PLS dataand is located at the beginning of a frame. In addition, the preamblecan carry PLS data described with reference to FIG. 66. That is, thepreamble can be considered to include both a symbol carrying the basicPLS data only and symbols carrying all PLS data described in FIG. 66,which can be modified by the designer.

Therefore, the apparatus for receiving broadcast signals according to anembodiment of the present invention can decode the preamble of eachsignal frame to identify the corresponding signal frame and acquire adesired broadcast service even when signal frames of different types,which are multiplexed in a super-frame, are received.

As described above with reference to FIG. 84, the preamble according toan embodiment of the present invention is a preamble signal in the timedomain and can include a scrambled cyclic prefix part, that is, a guardinterval and an OFDM symbol. The scrambled cyclic prefix partcorresponds to a guard interval and can be generated by combining someor all OFDM symbols and a specific sequence. Details are as described inFIG. 84.

In addition, the preamble according to an embodiment of the presentinvention can be generated through the procedure described withreference to FIGS. 94 and 95. Details are as described above.

FIG. 104 is a flowchart illustrating a method for receiving broadcastsignals according to an embodiment of the present invention.

The flowchart shown in FIG. 104 corresponds to a reverse process of thebroadcast signal transmission method according to an embodiment of thepresent invention, described with reference to FIG. 103.

The apparatus for receiving broadcast signals according to an embodimentof the present invention can receive the broadcast signals anddemodulate received broadcast signals using an OFDM scheme (S39000).Details are as described in FIG. 73 or 74.

The apparatus for receiving broadcast signals according to an embodimentof the present invention can parse a signal frame from the demodulatedbroadcast signals (S39100). Details are as described in FIG. 73 or 75.In this case, the signal frame can include DP data for carryingservices.

Subsequently, the apparatus for receiving broadcast signals according toan embodiment of the present invention can time-deinterleave the DP dataincluded in the parsed signal frame (S39200). Details are as describedin FIG. 73 or 76 and FIG. 80.

Then, the apparatus for receiving broadcast signals according to anembodiment of the present invention can demap the time-deinterleaved DPdata (S39300). Details are as described in FIG. 73 or 76 and FIG. 80.

The apparatus for receiving broadcast signals according to an embodimentof the present invention can decode the demapped DP data (S39400).Details are as described in FIG. 73 or 76 and FIG. 80.

As described above, the signal frame according to an embodiment of thepresent invention can include EAS information. In this case, the EASinformation can be transmitted through a specific data pipe included inthe signal frame according to design. Accordingly, the apparatus forreceiving broadcast signals according to an embodiment of the presentinvention can obtain the EAS information transmitted through the signalframe as necessary.

Furthermore, the apparatus for receiving broadcast signals according toan embodiment of the present invention can decode the preamble of eachsignal frame to identify the corresponding signal frame and obtain adesired broadcast service, as described above.

Moreover, signaling information included in the preamble according to anembodiment of the present invention can be decoded through the proceduredescribed with reference to FIG. 102. Details are as described above.

The present invention will not be limited only to the above-describedexemplary embodiments presented herein. And, therefore, as it isindicated in the scope of the appended claims, it will be apparent tothose skilled in the art that various modifications and variations canbe made in the present invention, and that such modifications andvariations cover the scope of the present invention.

MODE FOR CARRYING OUT THE PRESENT INVENTION

As described above, the present invention is described with respect tothe best mode for carrying out the present invention.

INDUSTRIAL APPLICABILITY

As described above, the present invention may be fully (or entirely) orpartially applied to digital broadcasting systems.

What is claimed is:
 1. A method of transmitting service data proceedingwith input data to output transmission unit data; encoding thetransmission unit data; interleaving the encoded transmission unit data;mapping the interleaved transmission unit data; building a signal frameincluding the mapped transmission unit data; modulating the signal frameby OFDM (Orthogonal Frequency Division Multiplex) scheme; inserting apreamble at a start of the signal frame in a time domain, andtransmitting a broadcast signal carrying the modulated signal frame andthe preamble, wherein the preamble includes a first preamble symbol anda second preamble symbol, and a sequence of the first preamble symbolare different from a sequence of the second preamble symbol in a timedomain, wherein the first preamble symbol includes a suffix in the timedomain which is obtained from a part of the first preamble symbol basedon a frequency shifting method, and wherein the second preamble symbolincludes a prefix in the time domain which is obtained from a part ofthe second preamble symbol based on a frequency shifting method.
 2. Themethod of claim 1, the method further comprising: MIMO encoding themapped transmission unit data, wherein the signaling data includesinformation on the MIMO encoding, which is applied to associatedtransmission unit data.
 3. The method of claim 1, the method furtherincludes: generating the preamble having a guard interval, wherein theguard interval is generated by combining a cyclic prefix of an OFDMsymbol of the preamble and a specific sequence.
 4. The method of claim3, wherein the specific sequence is a Binary chirp-like sequence.